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| TS4994 1W Differential Input/Output Audio Power Amplifier with Selectable Standby Differential inputs Near zero pop & click 100dB PSRR @ 217Hz with grounded inputs Operating from VCC = 2.5V to 5.5V 1W RAIL to RAIL output power @ Vcc=5V, THD=1%, F=1kHz, with 8 load 90dB CMRR @ 217Hz Ultra-low consumption in standby mode (10nA) Selectable standby mode (active low or active high Ultra fast startup time: 15ms typ. Available in DFN10 3x3, 0.5mm pitch & MiniSO8 All lead-free packages Pin Connections (top view) TS4994IQT - DFN10 STBY VIN STBY MODE VIN + BYPASS 1 2 3 4 5 10 9 8 7 6 VO+ VDD N/C GND VO- TS4994IST - MiniSO8 Description The TS4994 is an audio power amplifier capable of delivering 1W of continuous RMS output power into an 8 load @ 5V. Thanks to its differential inputs, it exhibits outstanding noise immunity. An external standby mode control reduces the supply current to less than 10nA. A STBY MODE pin allows the standby pin to be active HIGH or LOW (except in the MiniSO8 version). An internal thermal shutdown protection is also provided, making the device capable of sustaining shortcircuits. The device is equipped with Common Mode Feedback circuitry allowing outputs to be always biased at Vcc/2 regardless of the input common mode voltage. The TS4994 has been designed for high quality audio applications such as mobile phones and requires few external components. STBY VINVIN+ BYPASS 1 2 3 4 8 7 6 5 VO+ Vcc GND VO- Applications Mobile phones (cellular / cordless) Laptop / notebook computers PDAs Portable audio devices Order Codes Part Number TS4994IQT TS4994IST Temperature Range -40C to +85C -40C to +85C Package DFN10 MiniSO8 Packaging Tape & Reel Tape & Reel Marking K994 K994 April 2005 Revision 4 1/31 TS4994 Application Component Information 1 Application Component Information Components CS CB RFEED RIN CIN Functional Description Supply Bypass capacitor which provides power supply filtering. Bypass capacitor which provides half supply filtering. Feedback resistor which sets the closed loop gain in conjunction with RIN AV= Closed Loop Gain= RFEED/RIN. Inverting input resistor which sets the closed loop gain in conjunction with RFEED. Optional input capacitor making a high pass filter together with RIN. (fcl = 1 / (2 x Pi x RIN x CIN) Figure 1. Typical Application DFN10 Version VCC Rfeed1 20k 9 VCC Diff. input Cin1 + Rin1 2 VinGND + GND 220nF 20k Cin2 Rin2 4 Vin+ 5 Bypass Cb 1u + Bias Standby 220nF 20k Diff. Input + Optional Mode GND Stdby 1 GND 7 GND 3 Rfeed2 20k GND VCC GND VCC Figure 2. Typical Application Mini-SO8 Version VCC Rfeed1 20k 7 VCC + Diff. input - Cin1 Rin1 220nF 20k Cin2 Rin2 + 2 VinGND GND 3 Vin+ 4 Bypass Cb 1u + Bias Standby Stdby 220nF 20k Diff. Input + Optional GND GND 6 GND 1 Rfeed2 20k GNDVCC 2/31 + + + Cs 1u Vo+ 10 Vo6 8 Ohms + TS4994IQ Cs 1u Vo+ 8 Vo5 8 Ohms TS4994IS Absolute Maximum Ratings TS4994 2 Absolute Maximum Ratings Table 1. Key parameters and their absolute maximum ratings Symbol VCC Vi Toper Tstg Tj Rthja Pd ESD ESD Supply voltage 1 Input Voltage Operating Free Air Temperature Range Storage Temperature Maximum Junction Temperature Thermal Resistance Junction to Ambient DFN10 Mini-SO8 Power Dissipation Human Body Model Machine Model Latch-up Immunity Lead Temperature (soldering, 10sec) 3 2 Parameter Value 6 GND to VCC -40 to + 85 -65 to +150 150 120 215 internally limited 2 200 200 260 Unit V V C C C C/W W kV V mA C 1) All voltages values are measured with respect to the ground pin. 2) The magnitude of input signal must never exceed VCC + 0.3V / GND - 0.3V 3) The device is protected by a thermal shutdown active at 150C Table 2. Operating conditions Symbol VCC VSM Supply Voltage Standby Mode Voltage Input: Standby Active LOW Standby Active HIGH Standby Voltage Input: Device ON (VSM=GND) or Device OFF (VSM=VCC) Device OFF (VSM=GND) or Device ON (VSM=VCC) Thermal Shutdown Temperature Load Resistor Thermal Resistance Junction to Ambient DFN10 2 Mini-SO8 Parameter Value 2.5 to 5.5 VSM=GND VSM=VCC 1.5 VSTB VCC GND VSTB 0.4 1 150 Unit V V VSTB TSD RL RTHJA V C 8 80 190 C/W 1) The minimum current consumption (ISTANDBY) is guaranteed when V STB=GND or V CC (i.e. supply rails) for the whole temperature range. 2) When mounted on a 4-layer PCB. 3/31 TS4994 Electrical Characteristics 3 Electrical Characteristics Table 3. Electrical characteristics - VCC = +5V, GND = 0V, Tamb = 25C (unless otherwise specified) Symbol ICC Supply Current No input signal, no load Standby Current No input signal, Vstdby = VSM = GND, RL = 8 No input signal, Vstdby = VSM = VCC, RL = 8 Differential Output Offset Voltage No input signal, RL = 8 Input Common Mode Voltage CMRR -60dB Output Power THD = 1% Max, F= 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 850mW rms, Av = 1, 20Hz F 20kHz, RL = 8 Power Supply Rejection Ratio with Inputs Grounded1 F = 217Hz, R = 8, Av = 1, Cin = 4.7F, Cb =1F Vripple = 200mVPP Common Mode Rejection Ratio F = 217Hz, RL = 8, Av = 1, Cin = 4.7F, Cb =1F Vic = 200mVPP Signal-to-Noise Ratio (A Weighted Filter, Av = 2.5) (RL = 8, THD +N < 0.7%, 20Hz F 20kHz) Gain Bandwidth Product RL = 8 Output Voltage Noise, 20Hz F 20kHz, RL = 8 Unweighted, Av = 1 A weighted, Av = 1 Unweighted, Av = 2.5 A weighted, Av = 2.5 Unweighted, Av = 7.5 A weighted, Av = 7.5 Unweighted, Standby A weighted, Standby Wake-Up Time2 Cb =1F 0.6 0.8 1 0.5 Parameter Min. Typ. 4 Max. 7 Unit mA ISTANDBY 10 1000 nA Voo VICM Po THD + N 0.1 10 VCC- 0.9 mV V W % PSRRIG 100 dB CMRR 90 dB SNR GBP 100 2 dB MHz VN 6 5.5 12 10.5 33 28 1.5 1 15 VRMS TWU ms 1) Dynamic measurements - 20*log(rms(Vout)/rms (Vripple)). Vripple is the super-imposed sinus signal relative to Vcc. 2) Transition time from standby mode to fully operational amplifier. 4/31 Electrical Characteristics Table 4. TS4994 Electrical Characteristics: VCC = +3.3V (all electrical values are guaranteed with correlation measurements at 2.6V and 5V) GND = 0V, Tamb = 25C (unless otherwise specified) Parameter Supply Current No input signal, no load Standby Current No input signal, Vstdby = VSM = GND, RL = 8 No input signal, Vstdby = VSM = VCC, RL = 8 Differential Output Offset Voltage No input signal, RL = 8 Input Common Mode Voltage CMRR -60dB Output Power THD = 1% Max, F= 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 300mW rms, Av = 1, 20Hz F 20kHz, RL = 8 Power Supply Rejection Ratio with Inputs Grounded1 F = 217Hz, R = 8, Av = 1, Cin = 4.7F, Cb =1F Vripple = 200mVPP Common Mode Rejection Ratio F = 217Hz, RL = 8, Av = 1, Cin = 4.7F, Cb =1F Vic = 200mVPP Signal-to-Noise Ratio (A Weighted Filter, Av = 2.5) (RL = 8, THD +N < 0.7%, 20Hz F 20kHz) Gain Bandwidth Product RL = 8 Output Voltage Noise, 20Hz F 20kHz, RL = 8 Unweighted, Av = 1 A weighted, Av = 1 Unweighted, Av = 2.5 A weighted, Av = 2.5 Unweighted, Av = 7.5 A weighted, Av = 7.5 Unweighted, Standby A weighted, Standby Wake-Up Time2 Cb =1F 0.6 300 380 0.5 Min. Typ. 3 10 Max. 7 1000 Unit mA nA Symbol ICC ISTANDBY Voo VICM Po THD + N 0.1 10 VCC- 0.9 mV V mW % PSRRIG 100 dB CMRR 90 dB SNR GBP 100 2 dB MHz VN 6 5.5 12 10.5 33 28 1.5 1 15 VRMS TWU ms 1) Dynamic measurements - 20*log(rms(Vout)/rms (Vripple)). Vripple is the super-imposed sinus signal relative to Vcc. 2) Transition time from standby mode to fully operational amplifier. 5/31 TS4994 Table 5. Symbol ICC Supply Current No input signal, no load Standby Current No input signal, Vstdby = VSM = GND, RL = 8 No input signal, Vstdby = VSM = VCC, RL = 8 Differential Output Offset Voltage No input signal, RL = 8 Input Common Mode Voltage CMRR -60dB Output Power THD = 1% Max, F= 1kHz, RL = 8 Total Harmonic Distortion + Noise Po = 225mW rms, Av = 1, 20Hz F 20kHz, RL = 8 Power Supply Rejection Ratio with Inputs Grounded1 F = 217Hz, R = 8, Av = 1, Cin = 4.7F, Cb =1F Vripple = 200mVPP Common Mode Rejection Ratio F = 217Hz, RL = 8, Av = 1, Cin = 4.7F, Cb =1F Vic = 200mVPP Signal-to-Noise Ratio (A Weighted Filter, Av = 2.5) (RL = 8, THD +N < 0.7%, 20Hz F 20kHz) Gain Bandwidth Product RL = 8 Output Voltage Noise, 20Hz F 20kHz, RL = 8 Unweighted, Av = 1 A weighted, Av = 1 Unweighted, Av = 2.5 A weighted, Av = 2.5 Unweighted, Av = 7.5 A weighted, Av = 7.5 Unweighted, Standby A weighted, Standby Wake-Up Time2 Cb =1F Electrical Characteristics Electrical Characteristics - VCC = +2.6V, GND = 0V, Tamb = 25C (unless otherwise specified) Parameter Min. Typ. 3 Max. 7 Unit mA ISTANDBY 10 1000 nA Voo VICM Po THD + N 0.1 0.6 200 250 0.5 10 VCC0.9 mV V mW % PSRRIG 100 dB CMRR 90 dB SNR GBP 100 2 dB MHz VN 6 5.5 12 10.5 33 28 1.5 1 15 VRMS TWU ms 1) Dynamic measurements - 20*log(rms(Vout)/rms (Vripple)). Vripple is the super-imposed sinus signal relative to Vcc. 2) Transition time from standby mode to fully operational amplifier. 6/31 Electrical Characteristics Figure 3. Current consumption vs. power supply voltage 4.0 No load 3.5 Tamb=25C Current Consumption (mA) TS4994 Figure 6. Current consumption vs. standby voltage 3.0 2.5 2.0 1.5 1.0 0.5 0.0 0.0 Vcc = 2.6V No load Tamb=25C 0.6 1.2 1.8 2.4 Standby mode=0V Standby mode=2.6V 3.0 2.5 2.0 1.5 1.0 0.5 0.0 0 1 2 3 4 5 Power Supply Voltage (V) Current Consumption (mA) Standby Voltage (V) Figure 4. Current consumption vs. standby voltage 4.0 3.5 Current Consumption (mA) Figure 7. Differential DC output voltage vs. common mode input voltage 1000 Av = 1 Tamb = 25C 100 3.0 2.5 2.0 1.5 1.0 0.5 0.0 0 1 2 Standby mode=0V Voo (mV) Vcc=3.3V Vcc=2.5V Standby mode=5V 10 Vcc=5V 1 Vcc = 5V No load Tamb=25C 3 4 5 0.1 0.01 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 Standby Voltage (V) Common Mode Input Voltage (V) Figure 5. Current consumption vs. standby voltage 3.5 3.0 Figure 8. Power dissipation vs. output power 0.6 Current Consumption (mA) Power Dissipation (W) 2.5 2.0 1.5 1.0 0.5 0.0 0.0 Standby mode=0V Standby mode=3.3V RL=8 0.4 0.2 RL=16 Vcc=5V F=1kHz THD+N<1% Vcc = 3.3V No load Tamb=25C 0.6 1.2 1.8 2.4 3.0 0.0 0.0 0.2 0.4 0.6 Output Power (W) 0.8 1.0 Standby Voltage (V) 7/31 TS4994 Figure 9. Power dissipation vs. output power Electrical Characteristics Figure 12. Output power vs. power supply voltage 1.50 Output power @ 10% THD + N (W) 0.3 1.25 1.00 Power Dissipation (W) RL=8 0.2 Cb = 1F F = 1kHz BW < 125kHz Tamb = 25C 8 16 0.75 0.50 0.25 0.00 2.5 0.1 RL=16 Vcc=3.3V F=1kHz THD+N<1% 0.4 32 0.0 0.0 0.1 0.2 0.3 Output Power (W) 3.0 3.5 Vcc (V) 4.0 4.5 5.0 Figure 10. Power dissipation vs. output power 0.20 Vcc=2.6V F=1kHz THD+N<1% Figure 13. Output power vs. load resistance 1.0 THD+N=1% Cb = 1 F F = 1kHz BW < 125kHz Tamb = 25C Vcc=4V Power Dissipation (W) 0.15 Output power (W) 0.8 Vcc=5V Vcc=4.5V RL=8 0.10 0.6 0.4 0.05 RL=16 0.2 Vcc=3.5V Vcc=3V Vcc=2.5V 0.00 0.0 0.1 0.2 Output Power (W) 0.3 0.0 8 12 16 20 24 Load Resistance 28 32 Figure 11. Output power vs. power supply voltage 1.0 Output power @ 1% THD + N (W) Figure 14. Power derating curves 0.8 Cb = 1F F = 1kHz BW < 125kHz Tamb = 25C 8 DFN10 Package Power Dissipation (W) 1.5 with 4 layers PCB 1.0 0.6 16 0.4 0.5 AMR Value 0.2 32 0.0 2.5 3.0 3.5 Vcc (V) 4.0 4.5 5.0 0.0 0 25 50 75 100 125 Ambiant Temperature ( C) 8/31 Electrical Characteristics Figure 15. Power derating curves MiniSO8 Package Power Dissipation (W) TS4994 Figure 18. Open Loop gain vs. frequency 0 60 Gain 40 Gain (dB) 0.6 Nominal Value 0.4 -40 Phase () Phase () Phase () -80 20 Phase -120 0.2 AMR Value 0 Vcc = 2.6V ZL = 8 + 500pF Tamb = 25C 1 10 100 1000 -20 -160 0.0 0 25 50 75 100 125 -40 0.1 -200 10000 Ambiant Temperature ( C) Frequency (kHz) Figure 16. Open loop gain vs. frequency 0 60 Gain 40 Gain (dB) Figure 19. Close loop gain vs. frequency 10 Phase -40 Phase () 0 Gain 0 -40 20 Phase -120 Gain (dB) -80 -10 -80 0 Vcc = 5V ZL = 8 + 500pF Tamb = 25C 1 10 100 1000 -20 Vcc = 5V Av = 1 ZL = 8 + 500pF Tamb = 25C 1 10 100 1000 -120 -20 -160 -30 -160 -40 0.1 -200 10000 -40 0.1 -200 10000 Frequency (kHz) Frequency (kHz) Figure 17. Open loop gain vs. frequency 0 60 Gain 40 Gain (dB) Figure 20. Close loop gain vs. frequency 10 Phase -40 Phase () 0 Gain 0 -40 20 Phase -120 Gain (dB) -80 -10 -80 0 Vcc = 3.3V ZL = 8 + 500pF Tamb = 25C 1 10 100 1000 -20 Vcc = 3.3V Av = 1 ZL = 8 + 500pF Tamb = 25C 1 10 100 1000 -120 -20 -160 -30 -160 -40 0.1 -200 10000 -40 0.1 -200 10000 Frequency (kHz) Frequency (kHz) 9/31 TS4994 Figure 21. Close loop gain vs. frequency 10 Phase 0 Gain -40 Phase () Electrical Characteristics Figure 24. PSRR vs. frequency 0 0 -10 -20 -30 -40 -50 -60 -70 -80 Cb=1F -90 -100 -110 -120 Cb=0 Vcc = 2.6V Vripple = 200mVpp Inputs = Grounded Av = 1, Cin = 4.7F RL 8 Tamb = 25C Gain (dB) -10 -80 PSRR (dB) Cb=0.1F Cb=0.47F -20 Vcc = 2.6V Av = 1 ZL = 8 + 500pF Tamb = 25C 1 10 100 1000 -120 -30 -160 -40 0.1 -200 10000 20 100 Frequency (kHz) 1000 Frequency (Hz) 10000 20k Figure 22. PSRR vs. frequency 0 -10 -20 -30 PSRR (dB) Figure 25. PSRR vs. frequency 0 PSRR (dB) -40 -50 -60 -70 -80 -90 -100 -110 -120 20 Vcc = 5V Vripple = 200mVpp Inputs = Grounded Av = 1, Cin = 4.7F RL 8 Tamb = 25C -10 -20 -30 -40 -50 -60 -70 -80 -90 Cb=0 -100 -110 -120 Cb=0.1F Cb=0.47F Cb=1F Vcc = 5V Vripple = 200mVpp Inputs = Grounded Av = 2.5, Cin = 4.7F RL 8 Tamb = 25C Cb=0.1F Cb=0.47F Cb=1F Cb=0 100 1000 Frequency (Hz) 10000 20k 20 100 1000 Frequency (Hz) 10000 20k Figure 23. PSRR vs. frequency 0 -10 -20 -30 PSRR (dB) Figure 26. PSRR vs. frequency 0 PSRR (dB) -40 -50 -60 -70 -80 -90 -100 -110 -120 20 Vcc = 3.3V Vripple = 200mVpp Inputs = Grounded Av = 1, Cin = 4.7F RL 8 Tamb = 25C -10 -20 -30 -40 -50 -60 -70 -80 -90 Cb=0 -100 -110 -120 Cb=0.1F Cb=0.47F Cb=1F Vcc = 3.3V Vripple = 200mVpp Inputs = Grounded Av = 2.5, Cin = 4.7F RL 8 Tamb = 25C Cb=0.1F Cb=0.47F Cb=1F Cb=0 100 1000 Frequency (Hz) 10000 20k 20 100 1000 Frequency (Hz) 10000 20k 10/31 Electrical Characteristics Figure 27. PSRR vs. frequency 0 -10 -20 -30 PSRR (dB) TS4994 Figure 30. PSRR vs. frequency 0 -50 -60 -70 -80 -90 -100 -110 -120 20 Cb=0.1F Cb=0.47F PSRR (dB) -40 Vcc = 2.6V Vripple = 200mVpp Inputs = Grounded Av = 2.5, Cin = 4.7F RL 8 Tamb = 25C -10 -20 -30 -40 -50 -60 -70 -80 -90 Cb=0 -100 -110 -120 Vcc = 2.6V Vripple = 200mVpp Inputs = Floating Rfeed = 20k RL 8 Tamb = 25C Cb=0.1F Cb=0.47F Cb=1F Cb=1F Cb=0 100 1000 Frequency (Hz) 10000 20k 20 100 1000 Frequency (Hz) 10000 20k Figure 28. PSRR vs. frequency Figure 31. PSRR vs. common mode input voltage 0 0 -10 -20 -30 PSRR (dB) -50 -60 -70 -80 -90 -100 -110 -120 20 Cb=0.1F Cb=0.47F Cb=1F PSRR(dB) -40 Vcc = 5V Vripple = 200mVpp Inputs = Floating Rfeed = 20k RL 8 Tamb = 25C -20 -40 Vcc = 5V Vripple = 200mVpp Inputs Grounded F = 217Hz Av = 1 RL 8 Tamb = 25C Cb=0 -60 Cb=1F Cb=0.47F Cb=0.1F -80 Cb=0 -100 0 1 2 3 4 5 100 1000 Frequency (Hz) 10000 20k Common Mode Input Voltage (V) Figure 29. PSRR vs. frequency Figure 32. PSRR vs. common mode input voltage Vcc = 3.3V Vripple = 200mVpp Inputs Grounded F = 217Hz Av = 1 RL 8 Tamb = 25C Cb=0 0 -10 -20 -30 PSRR (dB) PSRR(dB) -40 -50 -60 -70 -80 -90 -100 -110 -120 20 Vcc = 3.3V Vripple = 200mVpp Inputs = Floating Rfeed = 20k RL 8 Tamb = 25C 0 -20 -40 -60 -80 Cb=0.1F Cb=0.47F Cb=1F Cb=1F Cb=0.47F Cb=0.1F Cb=0 -100 0.0 0.6 1.2 1.8 2.4 3.0 100 1000 Frequency (Hz) 10000 20k Common Mode Input Voltage (V) 11/31 TS4994 Figure 33. PSRR vs. common mode input voltage Electrical Characteristics Figure 36. CMRR vs. frequency 0 -20 0 Vcc = 2.5V Vripple = 200mVpp Inputs Grounded F = 217Hz Av = 1 RL 8 Tamb = 25C Cb=0 Cb=1F Cb=0.47F Cb=0.1F -10 -20 -30 CMRR (dB) PSRR(dB) -40 -60 -80 -40 -50 -60 -70 -80 -90 -100 -110 -120 Vcc = 2.6V Vic = 200mVpp Av = 1, Cin = 470F RL 8 Tamb = 25C Cb=1F Cb=0.47F Cb=0.1F Cb=0 -100 0.0 0.5 1.0 1.5 2.0 2.5 20 100 Common Mode Input Voltage (V) 1000 Frequency (Hz) 10000 20k Figure 34. CMRR vs. frequency 0 -10 -20 -30 CMRR (dB) Figure 37. CMRR vs. frequency 0 CMRR (dB) -40 -50 -60 -70 -80 -90 -100 -110 -120 20 Vcc = 5V Vic = 200mVpp Av = 1, Cin = 470F RL 8 Tamb = 25C -10 -20 Cb=1F Cb=0.47F Cb=0.1F Cb=0 -30 -40 -50 -60 -70 -80 -90 Vcc = 5V Vic = 200mVpp Av = 2.5, Cin = 470F RL 8 Tamb = 25C Cb=1F Cb=0.47F Cb=0.1F Cb=0 100 1000 Frequency (Hz) 10000 20k -100 20 100 1000 Frequency (Hz) 10000 20k Figure 35. PSRR vs. frequency 0 -10 -20 -30 CMRR (dB) Figure 38. CMRR vs. frequency 0 CMRR (dB) -40 -50 -60 -70 -80 -90 -100 -110 -120 20 Vcc = 3.3V Vic = 200mVpp Av = 1, Cin = 470F RL 8 Tamb = 25C -10 -20 Cb=1F Cb=0.47F Cb=0.1F Cb=0 -30 -40 -50 -60 -70 -80 -90 Vcc = 3.3V Vic = 200mVpp Av = 2.5, Cin = 470F RL 8 Tamb = 25C Cb=1F Cb=0.47F Cb=0.1F Cb=0 100 1000 Frequency (Hz) 10000 20k -100 20 100 1000 Frequency (Hz) 10000 20k 12/31 Electrical Characteristics Figure 39. CMRR vs. frequency 0 -10 -20 -30 CMRR (dB) TS4994 Figure 42. THD+N vs. output power 10 -40 -50 -60 -70 -80 -90 -100 20 THD + N (%) Vcc = 2.6V Vic = 200mVpp Av = 2.5, Cin = 470F RL 8 Tamb = 25C Cb=1F Cb=0.47F Cb=0.1F Cb=0 RL = 8 F = 20Hz Av = 1 1 Cb = 1F BW < 125kHz Tamb = 25C 0.1 Vcc=2.6V Vcc=3.3V Vcc=5V 0.01 100 1000 Frequency (Hz) 10000 20k 1E-3 1E-3 0.01 0.1 Output Power (W) 1 Figure 40. CMRR vs. common mode input voltage 0 Vcc=3.3V -20 CMRR(dB) Figure 43. THD+N vs. output power 10 RL = 8 F = 20Hz Av = 2.5 1 Cb = 1F BW < 125kHz Tamb = 25C 0.1 Vcc=2.6V Vcc=3.3V Vcc=5V Vcc=2.5V Vic = 200mVpp F = 217Hz Av = 1, Cb = 1F RL 8 Tamb = 25C THD + N (%) -40 -60 -80 -100 0.0 0.5 1.0 1.5 2.0 0.01 Vcc=5V 2.5 3.0 3.5 4.0 4.5 5.0 1E-3 1E-3 Common Mode Input Voltage (V) 0.01 0.1 Output Power (W) 1 Figure 41. CMRR vs. common mode input voltage Figure 44. THD+N vs. output power 10 0 Vcc=3.3V THD + N (%) -20 CMRR(dB) Vcc=2.5V Vic = 200mVpp F = 217Hz Av = 1, Cb = 0 RL 8 Tamb = 25C -40 -60 -80 RL = 8 F = 20Hz Av = 7.5 1 Cb = 1F BW < 125kHz Tamb = 25C Vcc=2.6V Vcc=3.3V Vcc=5V 0.1 0.01 -100 0.0 0.5 1.0 1.5 2.0 Vcc=5V 2.5 3.0 3.5 4.0 4.5 5.0 1E-3 0.01 0.1 Output Power (W) 1 Common Mode Input Voltage (V) 13/31 TS4994 Figure 45. THD+N vs. output power 10 RL = 8 F = 1kHz Av = 1 1 Cb = 1F BW < 125kHz Tamb = 25C Electrical Characteristics Figure 48. THD+N vs. output power 10 RL = 8 F = 20kHz Av = 1 Cb = 1F BW < 125kHz 1 Tamb = 25C Vcc=2.6V Vcc=3.3V Vcc=5V Vcc=2.6V Vcc=3.3V Vcc=5V THD + N (%) 0.1 0.01 1E-3 0.01 0.1 Output Power (W) 1 1E-3 0.01 0.1 Output Power (W) 1 Figure 46. THD+N vs. output power 10 RL = 8 F = 1kHz Av = 2.5 1 Cb = 1F BW < 125kHz Tamb = 25C Figure 49. THD+N vs. output power 10 RL = 8 F = 20kHz Av = 2.5 Cb = 1F BW < 125kHz 1 Tamb = 25C THD + N (%) 0.1 Vcc=2.6V Vcc=2.6V Vcc=3.3V Vcc=5V THD + N (%) Vcc=3.3V Vcc=5V 0.1 0.01 1E-3 0.01 0.1 Output Power (W) 1 1E-3 0.01 0.1 Output Power (W) 1 Figure 47. THD+N vs. output power 10 RL = 8 F = 1kHz Av = 7.5 1 Cb = 1F BW < 125kHz Tamb = 25C Vcc=2.6V Vcc=3.3V Figure 50. THD+N vs. output power 10 RL = 8 F = 20kHz Av = 7.5 Cb = 1F BW < 125kHz Tamb = 25C 1 THD + N (%) 0.1 Vcc=2.6V Vcc=3.3V Vcc=5V THD + N (%) Vcc=5V 0.1 0.01 1E-3 0.01 0.1 Output Power (W) 1 0.1 1E-3 0.01 0.1 Output Power (W) 1 14/31 THD + N (%) Electrical Characteristics Figure 51. THD+N vs. output power 10 RL = 16 F = 20Hz 1 Av = 1 Cb = 1F BW < 125kHz Tamb = 25C 0.1 Vcc=2.6V Vcc=3.3V TS4994 Figure 54. THD+N vs. output power 10 RL = 16 F = 1kHz Av = 7.5 1 Cb = 1F BW < 125kHz Tamb = 25C 0.1 Vcc=2.6V Vcc=3.3V THD + N (%) THD + N (%) Vcc=5V Vcc=5V 0.01 1E-3 1E-3 0.01 0.1 Output Power (W) 1 0.01 1E-3 0.01 0.1 Output Power (W) 1 Figure 52. THD+N vs. output power 10 RL = 16 F = 20Hz 1 Av = 7.5 Cb = 1F BW < 125kHz Tamb = 25C 0.1 Vcc=2.6V Vcc=3.3V Figure 55. THD+N vs. output power 10 RL = 16 F = 20kHz Av = 1 Cb = 1F 1 BW < 125kHz Tamb = 25C Vcc=2.6V Vcc=3.3V THD + N (%) Vcc=5V THD + N (%) Vcc=5V 0.1 0.01 1E-3 1E-3 0.01 0.1 Output Power (W) 1 0.01 1E-3 0.01 0.1 Output Power (W) 1 Figure 53. THD+N vs. output power 10 RL = 16 F = 1kHz 1 Av = 1 Cb = 1F BW < 125kHz Tamb = 25C 0.1 Vcc=2.6V Vcc=3.3V Figure 56. THD+N vs. output power 10 RL = 16 F = 20kHz Av = 7.5 Cb = 1F BW < 125kHz Tamb = 25C 1 Vcc=2.6V Vcc=3.3V THD + N (%) THD + N (%) Vcc=5V Vcc=5V 0.01 1E-3 1E-3 0.01 0.1 Output Power (W) 1 0.1 1E-3 0.01 0.1 Output Power (W) 1 15/31 TS4994 Figure 57. THD+N vs. output power 10 RL = 8 Vcc = 5V Av = 1 Cb = 0 BW < 125kHz Tamb = 25C Electrical Characteristics Figure 60. THD+N vs. output power 10 RL = 16 Vcc = 2.6V Av = 1, Cb = 0 1 BW < 125kHz Tamb = 25C 0.1 1 F=20kHz F=1kHz F=20kHz F=1kHz THD + N (%) 0.1 F=20Hz THD + N (%) F=20Hz 0.01 0.01 1E-3 1E-3 1E-3 0.01 0.1 Output Power (W) 1 0.01 Output Power (W) 0.1 Figure 58. THD+N vs. output power 10 RL = 8 Vcc = 2.6V Av = 1, Cb = 0 1 BW < 125kHz Tamb = 25C 0.1 Figure 61. THD+N vs. frequency 10 RL = 8 Av = 1 Cb = 1F 1 Bw < 125kHz Tamb = 25C THD + N (%) F=20kHz F=1kHz THD + N (%) Vcc=2.6V, Po=225mW 0.1 0.01 F=20Hz 0.01 Vcc=5V, Po=850mW 1E-3 1E-3 1E-3 0.01 Output Power (W) 0.1 20 100 1000 Frequency (Hz) 10000 20k Figure 59. THD+N vs. output power 10 RL = 16 Vcc = 5V Av = 1, Cb = 0 1 BW < 125kHz Tamb = 25C 0.1 Figure 62. THD+N vs. frequency 10 RL = 8 Av = 1 Cb = 0 1 Bw < 125kHz Tamb = 25C THD + N (%) F=20kHz F=1kHz THD + N (%) Vcc=2.6V, Po=225mW 0.1 F=20Hz 0.01 0.01 Vcc=5V, Po=850mW 1E-3 1E-3 1E-3 0.01 0.1 Output Power (W) 1 20 100 1000 Frequency (Hz) 10000 20k 16/31 Electrical Characteristics Figure 63. THD+N vs. frequency 10 RL = 8 Av = 7.5 Cb = 1F Bw < 125kHz 1 Tamb = 25C THD + N (%) TS4994 Figure 66. THD+N vs. frequency 10 RL = 16 Av = 7.5 Cb = 1F 1 Bw < 125kHz Tamb = 25C THD + N (%) Vcc=2.6V, Po=155mW Vcc=2.6V, Po=225mW 0.1 0.1 0.01 Vcc=5V, Po=850mW Vcc=5V, Po=600mW 0.01 20 100 1000 Frequency (Hz) 10000 20k 1E-3 20 100 1000 Frequency (Hz) 10000 20k Figure 64. THD+N vs. frequency Figure 67. SNR vs. power supply voltage with unweighted filter 110 RL=16 Signal to Noise Ratio (dB) 10 RL = 8 Av = 7.5 Cb = 0 Bw < 125kHz 1 Tamb = 25C THD + N (%) 105 100 95 90 Av = 2.5 85 Cb = 1F THD+N < 0.7% Tamb = 25C 80 2.5 3.0 RL=8 Vcc=2.6V, Po=225mW 0.1 Vcc=5V, Po=850mW 0.01 20 100 1000 Frequency (Hz) 10000 20k 3.5 4.0 4.5 5.0 Power Supply Voltage (V) Figure 65. THD+N vs. frequency 10 RL = 16 Av = 1 Cb = 1F 1 Bw < 125kHz Tamb = 25C THD + N (%) Figure 68. SNR vs. power supply voltage with a weighted filter 110 RL=16 105 100 RL=8 95 90 Av = 2.5 85 Cb = 1F THD+N < 0.7% Tamb = 25C 80 2.5 3.0 Vcc=2.6V, Po=155mW 0.1 0.01 Vcc=5V, Po=600mW 1E-3 20 100 1000 Frequency (Hz) 10000 20k Signal to Noise Ratio (dB) 3.5 4.0 4.5 5.0 Power Supply Voltage (V) 17/31 TS4994 Figure 69. Startup time vs. bypass capacitor Electrical Characteristics 20 Tamb=25C Vcc=5V Startup Time (ms) 15 Vcc=3.3V 10 5 Vcc=2.6V 0 0.0 0.4 0.8 1.2 1.6 Bypass Capacitor Cb ( F) 2.0 18/31 Application Information TS4994 4 Application Information 4.1 Differential configuration principle The TS4994 is a monolithic full-differential input/ output power amplifier. The TS4994 also includes a common mode feedback loop that controls the output bias value to average it at Vcc/2 for any DC common mode input voltage. This allows the device to always have a maximum output voltage swing, and by consequence, maximize the output power. Moreover, as the load is connected differentially compared to a single-ended topology, the output is four times higher for the same power supply voltage. The advantages of a full-differential amplifier are: l Very high PSRR (Power Supply Rejection Ratio). l High common mode noise rejection. l Virtually zero pop without additional circuitry, giving an faster start-up time compared to conventional single-ended input amplifiers. l Easier interfacing with differential output audio DAC. l No input coupling capacitors required thanks to common mode feedback loop. l In theory, the filtering of the internal bias by an external bypass capacitor is not necessary. But, to reach maximal performances in all tolerance situations, it's better to keep this option. The main disadvantage is: l As the differential function is directly linked to external resistors mismatching, in order to reach maximal performances of the amplifier paying particular attention to this mismatching is mandatory. 4.2 Gain in typical application schematic Typical differential applications are shown on the figures on page 2. In the flat region of the frequency-response curve (no Cin effect), the differential gain is expressed by the relation: Av diff = VO + - VO - R = feed Diff.Input + -Diff.Input - Rin where Rin = Rin1 = Rin2 and Rfeed = R feed1 = R feed2 . Note: For the rest of this chapter, Avdiff will be called Av to simplify the expression. 4.3 Common mode feedback loop limitations As explained previously, the common mode feedback loop allows the output DC bias voltage to be averaged at Vcc/2 for any DC common mode bias input voltage. However, due to VICM limitation of the input stage (see Electrical Characteristics on page 4), the common mode feedback loop can ensure its role only within a defined range. This range depends upon the values of Vcc, Rin and Rfeed (Av). To have a good estimation of the VICM value, we can apply this formula: Vcc x Rin + 2 x VIC x Rfeed (V) VICM = 2 x (Rin + Rfeed ) with VIC = Diff.Input + + Diff.Input - 2 (V) 19/31 TS4994 and the result of the calculation must be in the range: 0.6V VICM Vcc - 0.9V Application Information If the result of VICM calculation is not in the previous range, an input coupling capacitor must be used. Example: With Vcc=2.5V, R in=Rfeed=20k and V IC=2V, we found VICM=1.63V. This is higher than 2.5V0.9V=1.6V, so input coupling capacitors are required or you will have to change the VIC value. 4.4 Low and high frequency response In the low frequency region, Cin starts to have an effect. Cin forms, with Rin, a high-pass filter with a -3dB cut-off frequency. FCL is in Hz. 1 FCL = (Hz) 2 x x Rin x Cin In the high-frequency region, you can limit the bandwidth by adding a capacitor (Cfeed) in parallel with Rfeed. It forms a low-pass filter with a -3dB cut-off frequency. FCH is in Hz. 1 FCH = (Hz) 2 x x Rfeed x Cfeed While these bandwidth limitations are in theory attractive, in practice, because of low performance in terms of capacitor precision (and by consequence in terms of mismatching), they deteriorate the values of PSRR and CMRR. We will discuss the influence of mismatching on PSRR and CMRR performance in more detail in the following paragraphs. Example: A typical application with input coupling and feedback capacitor with FCL=50Hz and FCH=8kHz. We assume that the mismatching between Rin1,2 and C feed1,2 can be neglected. If we sweep the frequency from DC to 20kHz we observe the following with respect to the PSRR value: l From DC to 200Hz, the C in impedance decreases from infinite to a finite value and the Cfeed impedance is high enough to be neglected. Due to the tolerance of C in1,2, we must introduce a mismatch factor (Rin1 x Cin Rin2 x Cin2) that will decrease the PSRR performance. l From 200Hz to 5kHz, the C in impedance is low enough to be neglected when compare to Rin, and the C feed impedance is high enough to be neglected as well. In this range, we can reach the PSRR performance of the TS4994 itself. l From 5kHz to 20kHz, the C in impedance is low to be neglected when compared to Rin, and the Cfeed impedance decreases to a finite value. Due to tolerance of C feed1,2, we introduce a mismatching factor (R feed1 x C feed1 Rfeed2 x Cfeed2) that will decrease the PSRR performance. 20/31 Application Information 4.5 Calculating the influence of mismatching On PSRR performance: For this calculation, we consider that Cin and C feed have no influence. We use the same kind of resistor (same tolerance) and R is the tolerance value in %. TS4994 The following equation is valid for frequencies ranging from DC to about 1kHz. Above this frequency, parasitic effects start to be significant and a literal equation is not possible to write. The PSRR equation is (R in %): R x 100 PSRR 20 x Log 2 (10000 - R ) (dB) This equation doesn't include the additional performance provided by bypass capacitor filtering. If a bypass capacitor is added, it acts, together with the internal high output impedance bias, as a low-pass filter, and the result is a quite important PSRR improvement with a relatively small bypass capacitor. The complete PSRR equation (R in %, Cb in microFarad and F in Hz) is: R x 100 PSRR 20 x log ---------------------------------------------------------------------------------------------------2 2 2 ( 10000 - R ) x 1 + F x C b x 22.2 (dB) Example: With R=0.1% and Cb=0, the minimum PSRR would be -60dB. With a 100nF bypass capacitor, at 100Hz the new PSRR would be -93dB. This example is a worst case scenario, where each resistor has extreme tolerance and illustrates the fact that with only a small bypass capacitor, the TS4994 produce high PSRR performance. In addition, it's important to note that this is a theoretical formula. As the TS4994 has self-generated noise, you should consider that the highest practical PSRR reachable is about -110dB. It is therefore unreasonable to target a -120dB PSRR. The three following graphs show PSRR versus frequency and versus bypass capacitor Cb in worst-case condition (R=0.1%). Figure 70. PSRR vs. frequency worst case condition 0 -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 -110 -120 -130 -140 Vcc = 5V, Vripple = 200mVpp Av = 1, Cin = 4.7F R/R = 0.1%, RL 8 Tamb = 25C, Inputs = Grounded Figure 71. PSRR vs. frequency worst case condition 0 -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 -110 -120 -130 -140 Cb=0 PSRR (dB) PSRR (dB) Vcc = 3.3V, Vripple = 200mVpp Av = 1, Cin = 4.7F R/R = 0.1%, RL 8 Tamb = 25C, Inputs = Grounded Cb=0 Cb=0.1F Cb=0.1F Cb=1F 20 100 Cb=0.47F 1000 Frequency (Hz) 10000 20k Cb=1F 20 100 Cb=0.47F 1000 Frequency (Hz) 10000 20k 21/31 TS4994 Figure 72. PSRR vs. frequency worst case condition 0 -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 -110 -120 -130 -140 Application Information Vcc = 2.5V, Vripple = 200mVpp Av = 1, Cin = 4.7F R/R = 0.1%, RL 8 Tamb = 25C, Inputs = Grounded Cb=0 PSRR (dB) Cb=0.1F Cb=1F 20 100 Cb=0.47F 1000 Frequency (Hz) 10000 20k The two following graphs show typical application of TS4994 with four 0.1% tolerances and a random choice for them. Figure 73. PSRR vs. frequency with random choice condition 0 -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 -110 -120 -130 -140 Figure 74. PSRR vs. frequency with random choice condition 0 -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 -110 -120 -130 -140 Vcc = 5V, Vripple = 200mVpp Av = 1, Cin = 4.7F R/R 0.1%, RL 8 Tamb = 25C, Inputs = Grounded PSRR (dB) Vcc = 2.5V, Vripple = 200mVpp Av = 1, Cin = 4.7F R/R 0.1%, RL 8 Tamb = 25C, Inputs = Grounded PSRR (dB) Cb=0.1F Cb=0 Cb=0.1F Cb=0 Cb=1F 20 100 Cb=0.47F 1000 Frequency (Hz) 10000 20k Cb=1F 20 100 Cb=0.47F 1000 Frequency (Hz) 10000 20k CMRR performance For this calculation, we consider there to be no influence of Cin and Cfeed. Cb has no influence in the calculation of the CMRR. We use the same kind of resistor (same tolerance) and R is the tolerance value in %. The following equation is valid for frequencies ranging from DC to about 1kHz. Above this frequency, parasitic effects start to be significant and a literal equation is not possible to write. The CMRR equation is (R in %): R x 200 CMRR 20 x Log 2 (10000 - R ) (dB) Example: With R=1%, the minimum CMRR would be -34dB. With a DC Vic=2.5V, the DC differential output (Voo) which results is 50mV maximum. As this Voo is across the load, for an 8 load the extra consumption would be 50mV/8=6.2mA. 22/31 Application Information TS4994 With R=1%, the minimum CMRR would be -53dB that give Voo=5.6mV and an maximum extra consumption less than 700A. This example is of a worst case scenario where each resistor has extreme tolerance and illustrates the fact that for CMRR, good matching is essential. As with the PSRR, due to self-generated noise, the TS4994 CMRR limitation would be about -110dB. Figures 75 and 76 show CMRR versus frequency and versus bypass capacitor Cb in worst-case condition (R=0.1%). Figure 75. CMRR vs. frequency worst case condition 0 -10 -20 -30 -40 -50 -60 Vcc = 5V Vic = 200mVpp Av = 1, Cin = 470F R/R = 0.1%, RL 8 Tamb = 25C Figure 76. CMRR vs. frequency worst case condition 0 -10 -20 -30 -40 -50 -60 Vcc = 2.5V Vic = 200mVpp Av = 1, Cin = 470F R/R = 0.1%, RL 8 Tamb = 25C CMRR (dB) CMRR (dB) Cb=1F Cb=0 Cb=1F Cb=0 20 100 1000 Frequency (Hz) 10000 20k 20 100 1000 Frequency (Hz) 10000 20k Figures 77 and 78 show CMRR versus frequency for a typical application with four 0.1% tolerances and a random choice for them. Figure 77. CMRR vs. frequency with random choice condition 0 -10 -20 CMRR (dB) Figure 78. CMRR vs. frequency with random choice condition 0 -10 -20 CMRR (dB) -30 -40 -50 -60 -70 -80 -90 20 Vcc = 5V Vic = 200mVpp Av = 1, Cin = 470F R/R 0.1%, RL 8 Tamb = 25C -30 -40 -50 -60 -70 -80 -90 Vcc = 2.5V Vic = 200mVpp Av = 1, Cin = 470F R/R 0.1%, RL 8 Tamb = 25C Cb=1F Cb=0 Cb=1F Cb=0 100 1000 Frequency (Hz) 10000 20k 20 100 1000 Frequency (Hz) 10000 20k 23/31 TS4994 4.6 Power dissipation and efficiency Assumptions: l Load voltage and current are sinusoidal (Vout and Iout) l Supply voltage is a pure DC source (Vcc) Application Information Regarding the load we have: V out = V PEAK sint (V) and V out I out = ------------- (A) RL and VPE A K 2 P out = ---------------------- (W) 2RL Therefore, the average current delivered by the supply voltage is: ICC The power delivered by the supply voltage is: Psupply = Vcc Icc AVG (W) Then, the power dissipated by each amplifier is Pdiss = Psupply - Pout (W) 2 2V CC P diss = ----------------------- P out - P ou t RL and the maximum value is obtained when: Pdiss --------------------- = 0 P out and its value is: AVG VPEAK = 2 ------------------- (A) RL Pdiss max = Note: 2 Vcc 2 2RL (W) This maximum value is only dependent on power supply voltage and load values. The efficiency is the ratio between the output power and the power supply P out VPEAK = -------------------- = ---------------------P supply 4VCC The maximum theoretical value is reached when Vpeak = Vcc, so ---- = 78.5% 4 24/31 Application Information TS4994 The maximum die temperature allowable for the TS4994 is 125C. However, in case of overheating, a thermal shutdown set to 150C, puts the TS4994 in standby until the temperature of the die is reduced by about 5C. To calculate the maximum ambient temperature TAMB allowable, we need to know: l Power supply Voltage value, Vcc l Load resistor value, RL l The package type, RTHJA Example: Vcc=5V, RL=8, RTHJAFlip-Chip=100C/W (100mm2 copper heatsink). We calculate Pdissmax = 633mW. With TAMB = 125C - RTHJA x Pdiss (C) TAMB = 125-100x0.633=61.7C 4.7 Decoupling of the circuit Two capacitors are needed to correctly bypass the TS4994. A power supply bypass capacitor CS and a bias voltage bypass capacitor CB. CS has particular influence on the THD+N in the high frequency region (above 7kHz) and an indirect influence on power supply disturbances. With a value for CS of 1F, you can expect similar THD+N performances to those shown in the datasheet. In the high frequency region, if CS is lower than 1F, it increases THD+N and disturbances on the power supply rail are less filtered. On the other hand, if CS is higher than 1F, those disturbances on the power supply rail are more filtered. Cb has an influence on THD+N at lower frequencies, but its function is critical to the final result of PSRR (with input grounded and in the lower frequency region). 4.8 Wake-up Time: TWU When the standby is released to put the device ON, the bypass capacitor Cb will not be charged immediately. As Cb is directly linked to the bias of the amplifier, the bias will not work properly until the Cb voltage is correct. The time to reach this voltage is called the wake-up time or TWU and is specified in the tables found in Electrical Characteristics on page 4, with Cb=1F. During the wake-up time phase, the TS4994 gain is close to zero. After the wake-up time period, the gain is released and set to its nominal value. If Cb has a value other than 1F, please refer to the graph in Figure 69 on page 18 to establish the wakeup time value. 4.9 Shutdown time When the standby command is set, the time required to put the two output stages in high impedance and the internal circuitry in shutdown mode is a few microseconds. Note: In shutdown mode, Bypass pin and Vin+, Vin- pins are short-circuited to ground by internal switches. This allows a quick discharge of Cb and Cin capacitors. 25/31 TS4994 4.10 Pop performance Application Information In theory, due to a fully differential structure, the pop performance of the TS4994 should be perfect. However, due to Rin, Rfeed, and C in mismatching, some noise could remain at startup. In TS4994 we included a pop reduction circuitry reach the pop that is theoretical with mismatched components. With this circuitry, the TS4994 is close to zero pop for all common applications possible. In addition, when the TS4994 is set in standby, due to the high impedance output stage configuration in this mode, no pop is possible. 4.11 Single ended input configuration It's possible to use the TS4994 in a single-ended input configuration. However, input coupling capacitors areneeded in this configuration. The schematic in Figure 79 shows this configuration using the miniSO8 version of the TS4994 as example. Figure 79. Single ended input typical application VCC Rfeed1 20k 7 VCC Ve Cin1 + 220nF Cin2 + GND GND Rin1 20k Rin2 20k 2 Vin- - 3 Vin+ 4 Bypass + Bias Standby Stdby 220nF Optional Cb 1u GND 6 GND GND 1 Rfeed2 20k GND VCC The components calculations remain the same except for the gain. The new formula is: V - VO - Rfeed Av SE = O + = Ve Rin 26/31 + + Cs 1u Vo+ 8 Vo5 8 Ohms TS4994IS Application Information 4.12 Demoboard TS4994 A demoboard for the TS4994 is available, however it is designed only for the TS4994 in the DFN10 package. However, we can guarantee that all electrical parameters are similar except for the power dissipation. For more information about this demoboard, please refer to Application Note AN2013. Figure 80. Demoboard schematic Cn8 Vcc + C4 1uF/6V GND R2 22k/1% R4 22k/1% Cn3 J1 GND GND C5 100nF/10V 9 VCC Cn1 Pos. Input GND Neg. Input C1 R1 2 Vin- - Cn5 Vo+ 10 Vo6 Bias 100nF/10V 22k/1% 100nF/10V C2 Cn2 GND J2 Cn4 R3 22k/1% 4 Vin+ 5 Bypass C3 1uF/6V + + Standby Mode GND Stdby 1 Vcc Cn7 GND 7 TS4994DFN10 3 Cn6 Vcc 1 2 J3 1 2 3 GND J4 GND 3 GND Figure 81. Components location Figure 82. Top layer 27/31 TS4994 Figure 83. Bottom layer Application Information 28/31 Package Mechanical Data TS4994 5 Package Mechanical Data 5.1 MiniSO8 package 29/31 TS4994 5.2 DFN10 package Dimensions in millimeters unless otherwise indicated. Package Mechanical Data 3.0 10 3.0 0.35 0.8 1 0.25 0.5 * The Exposed Pad is connected to the Ground 30/31 Revision History TS4994 6 Revision History Date 01 Sept. 2003 01 Oct. 2004 01 Jan. 2005 17 Mar. 2005 2 3 Revision 1 First Release Curves updated in the document Update Mechanical Data on Flip-Chip Package Remove datas on Flip-Chip Package Description of Changes Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics. The ST logo is a registered trademark of STMicroelectronics All other names are the property of their respective owners (c) 2005 STMicroelectronics - All rights reserved STMicroelectronics group of companies Australia - Belgium - Brazil - Canada - China - Czech Republic - Finland - France - Germany - Hong Kong - India - Israel - Italy - Japan Malaysia - Malta - Morocco - Singapore - Spain - Sweden - Switzerland - United Kingdom - United States of America www.st.com 31/31 |
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