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ina326 ina327 sbos222 ?december 2001 www.ti.com description the ina326 is a high-performance, low-cost, precision in- strumentation amplifier with rail-to-rail input and output. it is a true single-supply instrumentation amplifier with very-low dc errors and input common-mode range that extends beyond the positive and negative rails. these features make them suitable for applications ranging from general-purpose to high-accuracy. excellent long-term stability and very low 1/f noise assure low offset voltage and drift throughout the life of the product. the ina326 is specified over the extended industrial tem- perature range, ?0 c to +85 c, with operation from ?0 c to +125 c. the ina327, with shutdown and synchronization, will be available q1 2002. features precision low offset: 125 v (max) low offset drift: 1 v/ c (max) excellent long-term stability very-low 1/f noise true rail-to-rail i/o input common-mode range: 20mv beyond rails wide output swing: within 10mv of rails supply range: single +2.7v to +5.5v small size micro package: msop-8 low cost production data information is current as of publication date. products conform to specifications per the terms of texas instruments standard warranty. production processing does not necessarily include testing of all parameters. copyright ?2001, texas instruments incorporated precision, rail-to-rail i/o instrumentation amplifier please be aware that an important notice concerning availability, standard warranty, and use in critical applications of texas instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. applications low-level transducer amplifier for bridges, load cells, thermocouples wide dynamic range sensor measurements high-resolution test systems weigh scales multi-channel data acquisition systems medical instrumentation general-purpose ina326 and ina327 related products product features ina114 50 v v os , 0.5na i b , 115db cmr, 3ma i q , 0.25 v/ c drift ina118 50 v v os , 1na i b , 120db cmr, 385 a i q , 0.5 v/ c drift ina122 250 v v os , ?0na i b , 85 a i q , rail-to-rail output, 3 v/ c drift ina128 50 v v os , 2na i b , 125db cmr, 750 a i q , 0.5 v/ c drift ina321 500 v v os , 0.5pa i b , 94db cmrr, 60 a i q , rail-to-rail output ina326 r 1 r 2 c 2 v in v in+ 7 v+ 4 v v o 5 6 2 1 8 3 g = 2(r 2 /r 1 ) i n a 3 2 7 i n a 3 2 6
ina326, ina327 2 sbos222 www.ti.com specified package temperature package ordering transport product package-lead designator (1) range marking number media, quantity ina326 msop-8 dgk 40 c to +85 c b26 ina326ea/250 tape and reel, 250 " """" ina326ea/2k5 tape and reel, 2500 " (2) msop-8 dgk 40 c to +125 c b26 ina326idgkt tape and reel, 250 " """" ina326idgkr tape and reel, 2500 ina327 (2) msop-10 dgs 40 c to +85 c b27 ina327ea/250 tape and reel, 250 " """" ina327ea/2k5 tape and reel, 2500 " (2) msop-10 dgs 40 c to +125 c b27 INA327IDGST tape and reel, 250 " """" ina327idgsr tape and reel, 2500 notes: (1) for the most current specifications and package information, refer to our web site at www.ti.com. (2) ina326i with 1 25 c range and ina327 available q1 2002 specifications of 125 c parts may differ. package/ordering information absolute maximum ratings (1) supply voltage .................................................................................. +5.5v signal input terminals: voltage (2) ......................................... 0.5v to (v+) + 0.5v current (2) ........................................................................ 10ma output short-circuit ................................................................. continuous operating temperature range ....................................... 40 c to +125 c storage temperature range .......................................... 65 c to +150 c junction temperature .................................................................... +150 c lead temperature (soldering, 10s) ............................................... +300 c note: (1) stresses above these ratings may cause permanent damage. exposure to absolute maximum conditions for extended periods may degrade device reliability. these are stress ratings only, and functional operation of the device at these or any other conditions beyond those specified is not implied. (2) input terminals are diode clamped to the power-supply rails. input signals that can swing more than 0.5v beyond the supply rails should be current limited to 10ma or less. electrostatic discharge sensitivity this integrated circuit can be damaged by esd. texas instruments recommends that all integrated circuits be handled with appropriate precautions. failure to observe proper han- dling and installation procedures can cause damage. esd damage can range from subtle performance degrada- tion to complete device failure. precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. 1 2 3 4 8 7 6 5 r 1 v+ v o r 2 r 1 v in v in+ v ina326 msop-8 1 2 3 4 5 10 9 8 7 6 r 1 v+ v o r 2 shutdown r 1 v in v in+ v sync ina327 (1) msop-10 top view pin configuration note: (1) ina327 expected q1 2002.
ina326, ina327 3 sbos222 www.ti.com electrical characteristics: v s = +2.7v to +5.5v boldface limits apply over the specified temperature range , t a = C 40 c to 85 c at t a = +25 c, r l = 10k ? , g = 100 (r 1 = 2k ? , r 2 = 100k ? ), external gain set resistors, and ia common = v s /2, with external 1khz filters, unless otherwise noted. ina326ea parameter condition min typ max units input offset voltage, rti v os v s = +5v, v cm = v s /2 30 125 v over temperature 185 v vs temperature dv os /dt 0.15 1 v/ c vs power supply psr v s = +2.7v to +5.5v, v cm = v s /2 20 4 v/v long-term stability see note (1) input impedance, differential 10 10 || 2 ? || pf common-mode 10 10 || 14 ? || pf input voltage range C 0.02 (v+) + 0.02 v safe input voltage 0.5 (v+) + 0.5 v common-mode rejection cmr v s = 5v, v cm = 0.02v to (v+) + 0.02v 100 110 db over temperature 94 db input bias current v cm = v s /2 bias current i b v s = 5v 0.2 2na vs temperature see typical characteristics offset current i os v s = 5v 0.2 2na noise voltage noise, rti r s = 0 ? , g = 100, r 1 = 2k ? , r 2 = 100k ? f = 10hz 44 nv/ hz f = 100hz 44 nv/ hz f = 1khz 44 nv/ hz f = 0.01hz to 10hz 1 vp-p voltage noise, rti r s = 0 ? , g = 10, r 1 = 20k ? , r 2 = 100k ? f = 10hz 120 nv/ hz f = 100hz 97 nv/ hz f = 1khz 97 nv/ hz f = 0.01hz to 10hz 4 vp-p current noise, rti f = 1khz 0.15 pa/ hz f = 0.1hz to 10hz 4.2 pap-p output ripple, v o filtered (2) see applications information gain gain equation g = 2(r 2 /r 1 ) range of gain < 0.1 > 10000 v/v gain error (3) g = 10, 100, v s = 5v, v o = 0.075v to 4.925v 0.25 0.5 % vs temperature g = 10, 100, v s = 5v, v o = 0.075v to 4.925v 10 60 ppm/ c nonlinearity g = 10, 100, v s = 5v, v o = 0.075v to 4.925v 0.01 0.024 % of fs output voltage output swing from rail r l = 100k ? 5mv r l = 10k ? , v s = 5v 75 10 mv over temperature 75 mv capacitive load drive 500 pf short-circuit current i sc 25 ma internal oscillator frequency of auto-correction 90 khz accuracy 20 % frequency response bandwidth (4) , 3db bw g = 1 to 1k 1 khz slew rate (4) sr v s = 5v, all gains, c l = 100pf filter limited settling time (4) , 0.1% t s 1khz filter, g = 1 to 1k, v o = 2v step, c l = 100pf 0.95 ms 0.01% 1.3 ms 0.1% 10khz filter, g = 1 to 1k, v o = 2v step, c l = 100pf 130 s 0.01% 160 s overload recovery (4) 1khz filter, 50% output overload, g = 1 to 1k 30 s 10khz filter, 50% output overload, g = 1 to 1k 5 s power supply specified voltage range +2.7 +5.5 v quiescent current i q i o = 0, diff v in = 0v, v s = 5v 2.4 3.4 ma over temperature 3.7 ma temperature range specified range 40 +85 c operating range 40 +125 c storage range 65 +150 c thermal resistance ja msop-8 surface mount 150 c/w notes: (1) 1000-hour life test at 150 c demonstrated randomly distributed variation in the range of measurement limits approximately 10 v. (2) see applications information section, figures 1 and 2. (3) does not include error and tcr of external gain-setting resistors. (4) dynamic respon se is limited by filtering. higher bandwidths can be achieved by adjusting the filter.
ina326, ina327 4 sbos222 www.ti.com typical characteristics at t a = 25 c, v s = +5v, gain = 100, r l = 10k ? with external 1khz filters, unless otherwise noted. gain vs frequency 1khz filter frequency (hz) 10 100 1k 10k 100k 1m gain (db) 80 60 40 20 0 20 40 g = 1k g = 100 g = 10 g = 1 gain vs frequency 10khz filter frequency (hz) 10 100 1k 10k 100k 1m gain (db) 80 60 40 20 0 20 40 g = 1k g = 100 g = 10 g = 1 cmr vs frequency 1khz filter frequency (hz) 10 100 1k 10k 100k 1m cmr (db) 160 140 120 100 80 60 40 20 g = 1k g = 100 g = 10 g = 1 cmr vs frequency 10khz filter frequency (hz) 10 100 1k 10k 100k 1m cmr (db) 160 140 120 100 80 60 40 20 g = 100 g = 10 g = 1 g = 1k input-referred voltage noise and input bias current noise vs frequency 10khz filter 1 10k 1k 100 10 1 0.1 0.01 0.001 10 100 1k 10k frequency (hz) input-referred voltage noise (nv/ hz) input bias current noise (pa/ hz) g = 1 g = 100 current noise (all gains) g = 10 g = 1000 power-supply rejection vs frequency frequency (hz) 10 100 1k 10k 100k psr (db) 120 100 80 60 40 20 0 g = 100, 1k g = 10 g = 1 filter frequency 10khz 1khz
ina326, ina327 5 sbos222 www.ti.com typical characteristics (cont.) at t a = 25 c, v s = +5v, gain = 100, r l = 10k ? with external 1khz filters, unless otherwise noted. input offset voltage vs warm-up time 1khz filter, g = 100 input offset voltage (20 v/div) 1 02 warm-up time (ms) input offset voltage vs warm-up time 10khz filter, g = 100 input offset voltage (20 v/div) 0.2 0.3 0 0.1 0.4 warm-up time (ms) small-signal response g = 1, 10, and 100 50mv/div 500 s/div 1khz filter 10khz filter small-signal step response g = 1000 50mv/div 500 s/div 1khz filter large-signal response g = 1 to 1000 2v/div 500 s/div 1khz filter 10khz filter 0.01hz to 10hz voltage noise 200nv/div 10s/div
ina326, ina327 6 sbos222 www.ti.com typical characteristics (cont.) at t a = 25 c, v s = +5v, gain = 100, r l = 10k ? with external 1khz filters, unless otherwise noted. offset voltage drift production distribution g = 100, 1000 offset voltage drift ( v/ c) 0.1 0.2 0.3 0.4 0.5 0.6 0.7 population offset voltage production distribution g = 100, 1000 offset voltage ( v) 37.5 25.0 12.5 0 12.5 25.0 37.5 50.0 62.5 75.0 87.5 100.0 population offset voltage drift production distribution g = 10 offset voltage drift ( v/ c) 1 2 3 4 5 6 7 population offset voltage production distribution g = 10 offset voltage ( v) 375 250 125 0 125 250 375 500 625 750 875 population offset voltage drift production distribution g = 1 offset voltage drift ( v/ c) 10 20 30 40 50 60 population offset voltage production distribution g = 1 offset voltage ( v) 6250 5000 3750 2500 1250 0 1250 2500 3750 5000 6250 population
ina326, ina327 7 sbos222 www.ti.com typical characteristics (cont.) at t a = 25 c, v s = +5v, gain = 100, r l = 10k ? with external 1khz filters, unless otherwise noted. gain error production distribution gain error (m%) 500 450 400 350 300 250 200 150 100 50 0 50 100 150 200 250 300 350 400 450 500 population input bias current vs temperature temperature ( c) 50 25 0 25 50 75 100 125 i b (na) 2.0 1.5 1.0 0.5 0 0.5 1.0 1.5 2.0 i b+ i b quiescent current vs temperature temperature ( c) 50 25 0 25 50 75 100 125 i q (ma) 3.0 2.5 2.0 1.5 1.0 0.5 0 v s = +2.7v v s = +5v output ripple spectrum g = 100 frequency (hz) 0 200k 400k 600k 800k 1m v out (dbv) v out ( v rms ) 60 70 80 90 100 110 120 130 140 1000 316 100 31.6 10 3.16 1 0.316 0.1
ina326, ina327 8 sbos222 www.ti.com ina326 v o filtered v o 6 g = 2(r 2 /r 1 ) f o = 1khz r o 470 ? c o (1) 0.22 f r 2 c 2 (1) 7 v+ 4 0.1 f v 5 single-supply operation ia common (2) ia common (2) ina326 r 1 r 1 v in v in+ v o filtered v o 6 2 1 8 3 g = 2(r 2 /r 1 ) f o = 1khz r o 470 ? c o (1) 0.22 f r 2 c 2 (1) 7 +2.5v 4 0.1 f 2.5v 5 dual-supply operation note: (1) c 2 and c o combine to form a 2-pole response that is 3db at 1khz. each individual pole is at 1.5khz. (2) output voltage is referenced to ia common (see text). note: (1) c 2 and c o combine to form a 2-pole response that is 3db at 1khz. each individual pole is at 1.5khz. (2) output voltage is referenced to ia common (see text). (3) output pedestal required for measurement near zero (see figure 5). 1 8 v in v in+ 2 3 (3) desired r 1 r 2 || c 2 gain ( ? )( ? || nf) 0.1 400k 20k || 5 0.2 400k 40k || 2.5 0.5 400k 100k || 1 1 400k 200k || 0.5 2 200k 200k || 0.5 5 80k 200k || 0.5 10 40k 200k || 0.5 20 20k 200k || 0.5 50 8k 200k || 0.5 100 4k 200k || 0.5 200 2k 200k || 0.5 500 2k 500k || 0.2 1000 2k 1m || 0.1 2000 2k 2m || 0.05 5000 2k 5m || 0.02 10000 2k 10m || 0.01 applications information figure 1 shows the basic connections required for operation of the ina326. a 0.1 f capacitor, placed close to and across the power supply pins is strongly recommended for highest accu- racy. r o c o is an output filter that minimizes auto-correction circuitry noise. this output filter may also serve as an anti- aliasing filter ahead of an analog-to-digital (a/d) converter. it is also optional based on desired precision. the output reference terminal is taken at the low side of r 2 (ia common ). the ina326 uses a unique internal topology to achieve excel- lent common-mode rejection (cmr). unlike conventional in- strumentation amplifiers, cmr is not affected by resistance in the reference connections or sockets. see inside the ina326 for further detail. to achieve best high-frequency cmr, mini- mize capacitance on pins 1 and 8. figure 1. basic connections. setting the gain the ina326 is a two-stage amplifier with each stage gain set by r 1 and r 2 , respectively (see figure 4, inside the ina326", for details.) overall gain is described by the equation: g r r = 2 2 1 (1) the stability and temperature drift of the external gain-setting resistors will affect gain by an amount that can be directly inferred from the gain equation (1). resistor values for commonly used gains are shown in figure 1. gain-set resistor values for best performance are different for +5v single-supply and for 2.5v dual-supply operation. optimum value for r 1 can be calculated by: r 1 = v in, max /12.5 a(2) where r 1 must be no less than 2k ? . desired r 1 r 2 || c 2 gain ( ? )( ? || nf) 0.1 400k 20k || 5 0.2 400k 40k || 2.5 0.5 400k 100k || 1 1 200k 100k || 1 2 100k 100k || 1 5 40k 100k || 1 10 20k 100k || 1 20 10k 100k || 1 50 4k 100k || 1 100 2k 100k || 1 200 2k 200k || 0.5 500 2k 500k || 0.2 1000 2k 1m || 0.1 2000 2k 2m || 0.05 5000 2k 5m || 0.02 10000 2k 10m || 0.01
ina326, ina327 9 sbos222 www.ti.com following this design procedure for r 1 produces the maxi- mum possible input stage gain for best accuracy and lowest noise. circuit layout and supply bypassing can affect performance. minimize the stray capacitance on pins 1 and 8. use recom- mended supply bypassing, including a capacitor directly from pin 7 to pin 4 (v+ to v ), even with dual (split) power supplies (see figure 1). dynamic performance the typical characteristic gain vs frequency shows that the ina326 has nearly constant bandwidth regardless of gain. this results from the bandwidth limiting from the recom- mended filters. noise performance internal auto-correction circuitry eliminates virtually all 1/f noise (noise that increases at low frequency) in gains of 100 or greater. noise performance is affected by gain-setting resistor values. follow recommendations in the setting gain section for best performance. total noise is a combination of input stage noise and output stage noise. when referred to the input, the total mid-band noise is: vnvhz nv hz g n =+ 44 800 / / (3) the output noise has some 1/f components that affect performance in gains less than 10. see typical characteristic input-referred voltage noise vs frequency. high-frequency noise is created by internal auto-correction circuitry and is highly dependent on the filter characteristics chosen. this may be the dominant source of noise visible when viewing the output on an oscilloscope. low cutoff frequency filters will provide lowest noise. figure 2 shows the typical noise performance as a function of cutoff frequency. applications sensitive to the spectral characteristics of high- frequency noise may require consideration of the spurious frequencies generated by internal clocking circuitry. spurs occur at approximately 90khz and its harmonics (see typical characteristic output spectrum ) which may be reduced by additional filtering below 1khz. insufficient filtering at pin 5 can cause nonlinearity with large output voltage swings (very near the supply rails). noise must be sufficiently filtered at pin 5 so that noise peaks do not hit the rail and change the average value of the signal. figure 2 shows guidelines for filter cutoff frequency. high-frequency noise c 2 and c o form filters to reduce internally generated auto- correction circuitry noise. filter frequencies can be chosen to optimize the tradeoff between noise and frequency response of the application, as shown in figure 2. the cutoff frequen- cies of the filters are generally set to the same frequency. figure 2 shows the typical output noise for four gains as a function of the 3db cutoff frequency of the combined two- pole response. this is equal to the 1.5db response fre- quency of each of the 1-pole filters. small signals may exhibit the addition of internally generated auto-correction circuitry noise at the output. this noise, combined with broadband noise, becomes most evident in higher gains with filters of wider bandwidth. input bias current return path the input impedance of the ina326 is extremely high approximately 10 10 ? . however, a path must be provided for the input bias current of both inputs. this input bias current is approximately 0.2na. high input impedance means that this input bias current changes very little with varying input voltage. input circuitry must provide a path for this input bias current for proper operation. figure 3 shows provision for an input bias current path in a thermocouple application. without a bias current path, the inputs will float to an undefined poten- tial and the output voltage may not be valid. figure 2. total output noise vs filter cutoff frequency. total output noise vs filter cutoff frequency 100 1 10 1k 10k required filter cutoff frequency (hz) total output noise ( v rms ) 1k 100 10 1 g = 10 g = 1 g = 100 g = 1000 ina326 thermocouple 5 figure 3. providing input bias current return path.
ina326, ina327 10 sbos222 www.ti.com input common-mode range common instrumentation amplifiers do not respond linearly with common-mode signals near the power-supply rails, even if rail-to-rail op amps are used. the ina326 uses a unique topology to achieve true rail-to-rail input behavior (see inside the ina326 ). the linear input voltage range of each input terminal extends to 20mv beyond the rails. the ina326 uses a new, unique internal circuit topology that provides true rail-to-rail input. unlike other instrumen- tation amplifiers, it can linearly process inputs up to 20mv beyond the power-supply rails. conventional instrumenta- tion amplifier circuits cannot deliver such performance, even if rail-to-rail op amps are used. the ability to reject common-mode signals is derived in most instrumentation amplifiers through a combination of amplifier cmr and accurately matched resistor ratios. the ina326 converts the input voltage to a current. current- mode signal processing provides rejection of common- mode input voltage and power supply variation without accurately matched resistors. a simplified diagram shows the basic circuit function. the differential input voltage, v in + v in is applied across r 1 . the signal-generated current through r 1 comes from a1 and a2 s output stages. a2 combines the current in r 1 with a mirrored replica of the current from a1. the result- ing current in a2 s output and associated current mirror is two times the current in r 1 . this current flows in (or out) of pin 5 into r 2 . the resulting gain equation is: g r r = 2 2 1 amplifiers a1, a2 and their associated mirrors are pow- ered from internal charge-pumps that provide voltage supplies that are beyond the positive and negative supply rails. as a result, the voltage developed on r 2 can actually swing 20mv beyond the external power supply rails. a3 provides a buffered output of the voltage on r 2 . a3 s input stage is also operated from the charge-pumped power supplies for true rail-to-rail operation. figure 4. simplified circuit diagram. inside the ina326 input protection the inputs of the ina326 are protected with internal diodes connected to the power-supply rails. these diodes will clamp the applied signal to prevent it from damaging the input circuitry. if the input signal voltage can exceed the power supplies by more than 0.5v, the input signal current should be limited to less than 10ma to protect the internal clamp diodes. this can generally be done with a series input resistor. some signal sources are inherently current-limited and do not require limiting resistors. a1 v+ v current mirror current mirror i r1 i r1 i r1 r 1 r 2 c 2 v o v in v in+ i r1 2i r1 2i r1 2i r1 2i r1 2i r1 a3 a2 ia common 0.1 f current mirror current mirror
ina326, ina327 11 sbos222 www.ti.com figure 5. output range pedestal. figure 6. high-side shunt measurement of current load. figure 7. low-side shunt measurement of current load. figure 8. output referenced to v ref /2. figure 9. output from pin 5 to allow swing beyond the rail. filtering filtering can be adjusted through selection of r 2 c 2 and r o c o for the desired tradeoff of noise and bandwidth. adjust- ment of these components will result in more or less ripple due to auto-correction circuitry noise and will also affect broadband noise. filtering limits slew rate, settling time, and output overload recovery time. it is generally desirable to keep the resistance of r o relatively low to avoid dc gain error created by the subsequent stage. this may result in relatively high values for c o to produce the desired filter response. the impedance of r o c o can be scaled higher to produce smaller capacitor values if the load impedance is very high. certain capacitor types greater than 0.1 f may have dielec- tric absorption effects that can significantly increase settling time in high-accuracy applications (settling to 0.01%). polypro- pylene, polystyrene, and polycarbonate types are generally good. certain high-k ceramic types may produce slow settling tails. settling time to 0.1% is not generally affected by high-k ceramic capacitors. electrolytic types are not recommended for c 2 and c o . r 1 r 2 5 r 0 r 2 c 2 c 0 v ref = 10v to 5v g = 2 (r 2 || r 2 )/r 1 ina326 r 2 and r 2 are chosen to create a small pedestal voltage (e.g., 100mv). gain is determined by the parallel combination of r 2 and r 2 . ina326 +5v i l 5 r o r s r 1 r 2 c 2 c o note: connection point of v+ will include ( ) or exclude ( ) quiescent current in the measurement as desired. output pedestal required for measurements near zero (see figure 5). r s must be chosen so that the input voltage does not exceed 20mv beyond the rail. ina326 +5v i l r s r o 5 c 2 c o r 2 r 1 note: connection point of v will include ( ) or exclude ( ) quiescent current in the measurement as desired. output pedestal required for measurements near zero (see figure 5). r s must be chosen so that the input voltage does not exceed 20mv beyond the rail. 2k ? 200k ? 200k ? v ref r o 5 c o c 2 v ref ina326 a/d converter g = 2(200k ? || 200k ? )/2k ? = 100 ina326 +5v nc (1) +15v 15v opa277 v d c 2 r 2 r 1 v cm 5 (2) note: (1) nc denotes no connection. (2) typical swing capability 20mv to +5v + 20mv.
ina326, ina327 12 sbos222 www.ti.com v s v v+ v v+ r 19 100k ? r 20 5k ? pot r 17 5k ? pot r 2 100k ? r diff 1m ? differentiator tc: 100ms to 1s r 1 100k ? c 8 0.1 f r 25 10k ? r 22 10k ? r 23 10k ? r 21 10k ? proportional error amplifier bias generator loop gain adjust set temp gain = 100v/v integrator tc: 1s to 10s 1/4 opa4340 1/4 opa4340 1/2 opa2340 1/4 opa4340 1/4 opa4340 c int 1 f r int 10m ? r 18 10k ? r 15 200 ? r 16 2k ? pot c 3 1nf v bias v bias v bias v s v s v bias common output to tec driver common +5v input v bias v bias c diff 1 f summing amplifier ina326 v o 6 r 14 10k ? r 13 20 ? r 10 1k ? c 7 22nf r 8 100k ? r 9 2k ? r 7 1k ? pot r 11 14.3k ? r 12 15k ? r therm 10k ? r 6 9.53k ? c 5 1nf r 5 20k ? r 4 20k ? c 2 470nf c 6 10 f ref1004-2.5 d 1 7 v+ 4 0.1 f v 5 8 8 4 1 in+ in 3 2 + c 4 10 f + 1/2 opa2340 v s v s c 1 1nf figure 4. single-supply pid temperature control loop.
ina326, ina327 13 sbos222 www.ti.com package drawings mpds028b june 1997 revised september 2001 dgk (r-pdso-g8) plastic small-outline package 0,69 0,41 0,25 0,15 nom gage plane 4073329/c 08/01 4,98 0,25 5 3,05 4,78 2,95 8 4 3,05 2,95 1 0,38 1,07 max seating plane 0,65 m 0,08 0 C 6 0,10 0,15 0,05 notes: a. all linear dimensions are in millimeters. b. this drawing is subject to change without notice. c. body dimensions do not include mold flash or protrusion. d. falls within jedec mo-187
ina326, ina327 14 sbos222 www.ti.com package drawings (cont.) mpds035a january 1998 revised september 2001 dgs (s-pdso-g10) plastic small-outline package 0,69 0,41 0,25 0,15 nom gage plane 4073272/b 08/01 4,98 0,17 6 3,05 4,78 2,95 10 5 3,05 2,95 1 0,27 0,15 0,05 1,07 max seating plane 0,10 0,50 m 0,08 0 C 6 notes: a. all linear dimensions are in millimeters. b. this drawing is subject to change without notice. c. body dimensions do not include mold flash or protrusion. a. falls within jedec mo-187
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