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features description tpa2000d2 slos291f ? march 2000 ? revised march 2007 2-w filterless stereo class-d audio power amplifier short-circuit protection (short to battery, ground, and load) modulation scheme optimized to operate without a filter -40c to 85c operating temperature range 2 w into 3- w speakers (thd+n< 0.4%) < 0.08% thd+n at 1 w, 1 khz, into 4- w load extremely efficient third generation 5-v class-d technology: ? low supply current (no filter) . . . 8 ma ? low supply current (filter) . . . 15 ma ? low shutdown current . . . 1 a ? low noise floor . . . 56 v rms ? maximum efficiency into 3 w , 65-70% ? maximum efficiency into 8 w , 75-85% ? 4 internal gain settings . . . 8-23.5 db ? psrr . . . -77 db integrated depop circuitry the tpa2000d2 is the third generation 5-v class-d amplifier from texas instruments. improvements to previous generation devices include: lower supply current, lower noise floor, better efficiency, four different gain settings, smaller packaging, and fewer external components. the most significant advancement with this device is its modulation scheme that allows the amplifier to operate without the output filter. eliminating the output filter saves the user approximately 30% in system cost and 75% in pcb area. the tpa2000d2 is a monolithic class-d power ic stereo audio amplifier, using the high switching speed of power mosfet transistors. these transistors reproduce the analog signal through high-frequency switching of the output stage. the tpa2000d2 is configured as a bridge-tied load (btl) amplifier capable of delivering greater than 2 w of continuous average power into a 3- w load at less than 1% thd+n from a 5-v power supply in the high fidelity range (20 hz to 20 khz). with 1 w being delivered to a 4- w load at 1 khz, the typical thd+n is less than 0.08%. a btl configuration eliminates the need for external coupling capacitors on the output. low supply current of 8 ma makes the device ideal for battery-powered applications. protection circuitry increases device reliability: thermal, over-current, and under-voltage shutdown. efficient class-d modulation enables the tpa2000d2 to operate at full power into 3- w loads at an ambient temperature of 85c. available options (1) packaged device t a tssop (pw) tssop (pwp) (2) ?40c to 85c tpa2000d2pw tpa2000d2pwp (1) for the most current package and ordering information, see the package option addendum at the end of this document, or see the ti web site at www.ti.com. (2) the pwp package is available taped and reeled. to order a taped and reeled part, add the suffix r to the part number (e.g., tpa2000d2pwpr). please be aware that an important notice concerning availability, standard warranty, and use in critical applications of texas instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. production data information is current as of publication date. copyright ? 2000?2007, texas instruments incorporated products conform to specifications per the terms of the texas instruments standard warranty. production processing does not necessarily include testing of all parameters. www.ti.com 12 3 4 5 6 7 8 9 10 11 12 2423 22 21 20 19 18 17 16 15 14 13 pgnd loutn gain0 pv dd linn agndcosc rinn pv dd shutdown routn pgnd pgndloutp bypass pv dd linpv dd roscrinp pv dd gain1routp pgnd pw or pwp p ackage (t op view)
tpa2000d2 slos291f ? march 2000 ? revised march 2007 these devices have limited built-in esd protection. the leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the mos gates. 2 submit documentation feedback www.ti.com gate drive _ + gate drive _+ _+ _ + gain adjust gain adjust start-up protection logic oc detect oc detect thermal v dd ok ramp generator biases and references gate drive _ + gate drive _+ _+ _ + gain adjust gain adjust gain 2 agnd v dd v dd pv dd rinn routnpgnd pv dd routppgnd pv dd loutppgnd pv dd loutnpgnd rinp shutdown gain1gain0 coscrosc bypass linp linn
absolute maximum ratings tpa2000d2 slos291f ? march 2000 ? revised march 2007 terminal function terminal i/o description name no. agnd 6 - analog ground bypass 22 i tap to voltage divider for internal midsupply bias generator used for analog reference. a capacitor connected to this terminal sets the oscillation frequency in conjunction with rosc. for cosc 7 i proper operation, connect a 220 pf capacitor from cosc to ground. gain0 3 i bit 0 of gain control (ttl logic level) gain1 15 i bit 1 of gain control (ttl logic level) linn 5 i left channel negative differential audio input linp 20 i left channel positive differential audio input loutn 2 o left channel negative audio output loutp 23 o left channel positive audio output 1, 24 - power ground for left channel h-bridge pgnd 12, 13 - power ground for right channel h-bridge 4, 21 - power supply for left channel h-bridge pv dd 9, 16 - power supply for right channel h-bridge rinn 8 i right channel negative differential audio input rinp 17 i right channel positive differential audio input a resistor connected to this terminal sets the oscillation frequency in conjunction with cosc. for rosc 18 i proper operation, connect a 120 k w resistor from rosc to ground. routn 11 o right channel negative audio output routp 14 o right channel positive output places the amplifier in shutdown mode if a ttl logic low is placed on this terminal; normal operation if shutdown 10 i a ttl logic high is placed on this terminal. v dd 19 - analog power supply over operating free-air temperature range (unless otherwise noted) (1) unit v dd , pv dd supply voltage -0.3 v to 6 v v i input voltage -0.3 v to v dd +0.3 v continuous total power dissipation see dissipation rating table t a operating free-air temperature range -40c to 85c t j operating junction temperature range -40c to 150c t stg storage temperature range -65c to 150c lead temperature 1,6 mm (1/16 inch) from case for 10 seconds 260c (1) stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. these are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under recommended operating conditions is not implied. exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. dissipation rating table t a 25c derating factor t a = 70c t a = 85c package power rating above t a = 25c power rating power rating pw 1.04 w 8.34 mw/c 0.67 w 0.54 w pwp 2.7 w 21.8 mw/c 1.7 w 1.4 w 3 submit documentation feedback www.ti.com
recommended operating conditions electrical characteristics operating characteristics tpa2000d2 slos291f ? march 2000 ? revised march 2007 min typ max unit v dd , pv dd supply voltage 4.5 5.5 v v ih high-level input voltage gain0, gain1, shutdown 2 v v il low-level input voltage gain0, gain1, shutdown 0.8 v r osc oscillator resistance 120 k w c osc oscillator capacitance 220 pf f s switching frequency 200 300 khz t a operating free-air temperature -40 85 c t a = 25c, v dd = pv dd = 5 v (unless otherwise noted) parameter test conditions min typ max unit | v oo | output offset voltage (measured differentially) v i = 0 v 25 mv psrr power supply rejection ratio v dd =pv dd = 4.5 v to 5.5 v -77 db i ih high-level input current v dd =pv dd = 5.5 v, v i = v dd = pv dd 1 a i il low-level input current v dd =pv dd = 5.5 v, v i = 0 v 1 a i dd supply current no filter (with or without speaker load) 8 10 ma i dd supply current with filter, l = 22 h, c = 1 f 15 ma i dd(sd) supply current, shutdown mode 1 15 a t a = 25c, v dd = pv dd = 5 v, r l = 4 w , gain = 8 db (unless otherwise noted) parameter test conditions min typ max unit p o output power thd = 0.1%, f = 1 khz, r l = 3 w 2 w thd+n total harmonic distortion plus noise p o = 1 w, f = 20 hz to 20 khz <0.5% b om maximum output power bandwidth thd = 5% 20 khz k svr supply ripple rejection ratio f = 1 khz, c (bypass) = 0.4 f -60 db snr signal-to-noise ratio 87 dbv integrated noise floor 20 hz to 20 khz, no input 56 v z i input impedance >20 k w table 1. gain settings amplifier gain input impedance (db) (k w ) gain1 gain0 typ typ 0 0 8 104 0 1 12 74 1 0 17.5 44 1 1 23.5 24 4 submit documentation feedback www.ti.com
typical characteristics test set-up for graphs tpa2000d2 slos291f ? march 2000 ? revised march 2007 table of graphs figure h efficiency vs output power 2, 3 fft at 1.5 w output power vs frequency 4 vs output power 5-7 thd+n total harmonic distortion plus noise vs frequency 8, 9 crosstalk vs frequency 10 power supply rejection ratio vs frequency 11 the thd+n measurements shown do not use an lc output filter, but use a low pass filter with a cutoff frequency of 20 khz so the switching frequency does not dominate the measurement. this is done to ensure that the thd+n measured is just the audible thd+n. the thd+n measurements are shown at the highest gain for worst case. the lc output filter used in the efficiency curves (figure 2 and figure 3 ) is shown in figure 1 . l1 = l2 = 22 h (dcr = 110 m w , part number = scd0703t-220 m-s, manufacturer = gci) c1 = c2 = 1 f the ferrite filter used in the efficiency curves (figure 2 and figure 3 ) is shown in figure 1 , where l is a ferrite bead. l1 = l2 = ferrite bead (part number = 2512067007y3, manufacturer = fair-rite) c1 = c2 = 1 nf figure 1. class-d output filter 5 submit documentation feedback www.ti.com c2 c1 l1 l2 out out+
typical characteristics tpa2000d2 slos291f ? march 2000 ? revised march 2007 efficiency efficiency vs vs output power output power figure 2. figure 3. fft at 1.5 w output power vs frequency figure 4. 6 submit documentation feedback www.ti.com 0 10 20 30 40 50 60 70 80 90 0 0.2 0.4 0.6 0.8 1 1.2 no filter ferrite bead filter lc filter class?ab r l = 8 w, multimedia speaker v dd = 5 v efficiency ? % p o ? output power ? w 0 10 20 30 40 50 60 70 80 0 0.5 1 1.5 2 ferrite bead filter notebook speaker class?ab efficiency ? % p o ? output power ? w lc filter r l = 3 w, notebook pc speaker v dd = 5 v ?140 +0 ?120 ?100 ?80 ?60 ?40 ?20 0 24k 2k 4k 6k 8k 10k 12k 14k 16k 18k 20k 22k power ? vdb f ? frequency ? hz v dd = 5 v , gain = 8 db,f = 1 khz, p o = 1.5 w , bandwidth = 20 hz to 22 khz,16386 frequency bins
tpa2000d2 slos291f ? march 2000 ? revised march 2007 typical characteristics (continued) total harmonic distortion plus noise total harmonic distortion plus noise vs vs output power output power figure 5. figure 6. total harmonic distortion plus noise total harmonic distortion plus noise vs vs output power frequency figure 7. figure 8. 7 submit documentation feedback www.ti.com 0.01 0.1 1 10 10 m thd+n ? t otal harmonic distortion ? % 100 m 1 2 3 p o ? output power ? w v dd = 5 v gain = 23.5 dbr l = 3 w 1 khz 20 khz 20 hz 1 khz 20 khz 20 hz v dd = 5 v gain = 23.5 dbr l = 4 w 0.1 0.01 10 m 100 m 1 10 1 2 3 thd+n ? t otal harmonic distortion ? % p o ? output power ? w 1 khz 0.1 0.01 10 m 100 m 1 10 1 2 thd+n ? t otal harmonic distortion ? % p o ? output power ? w v dd = 5 v gain = 23.5 dbr l = 8 w 20 hz 20 khz 0.1 0.01 20 100 1 k f ? frequency ? hz 10 10 k 20 k 0.2 w 0.75 w 1.5 w thd+n ? t otal harmonic distortion ? % v dd = 5 v gain = 23.5 dbr l = 4 w 1
tpa2000d2 slos291f ? march 2000 ? revised march 2007 typical characteristics (continued) total harmonic distortion plus noise vs frequency figure 9. crosstalk power supply rejection ratio vs vs frequency frequency figure 10. figure 11. 8 submit documentation feedback www.ti.com 0.1 0.01 20 100 1 k 1 10 20 k f ? frequency ? hz 0.1 w 1 w 0.5 w thd+n ? t otal harmonic distortion ? % v dd = 5 v gain = 23.5 dbr l = 8 w f ? frequency ? hz crosstalk ? db ?70 ?60 ?50 ?40 ?30 1 10 100 1 k 10 k 100 k left to right right to left ?90 ?80 ?70 ?60 ?50 ?40 ?30 10 100 1 k 10 k 100 k f ? frequency ? hz psrr ? power supply rejection ratio ? db
application information eliminating the output filter with the tpa2000d2 effect on audio traditional class-d modulation scheme tpa2000d2 modulation scheme tpa2000d2 slos291f ? march 2000 ? revised march 2007 this section focuses on why the user can eliminate the output filter with the tpa2000d2. the class-d amplifier outputs a pulse-width modulated (pwm) square wave, which is the sum of the switching waveform and the amplified input audio signal. the human ear acts as a band-pass filter such that only the frequencies between approximately 20 hz and 20 khz are passed. the switching frequency components are much greater than 20 khz, so the only signal heard is the amplified input audio signal. the traditional class-d modulation scheme, which is used in the tpa005dxx family, has a differential output where each output is 180 degrees out of phase and changes from ground to the supply voltage, v dd . therefore, the differential prefiltered output varies between positive and negative v dd , where filtered 50% duty cycle yields 0 volts across the load. the traditional class-d modulation scheme with voltage and current waveforms is shown in figure 12 . note that even at an average of 0 volts across the load (50% duty cycle), the current to the load is high causing high loss, thus causing a high supply current. figure 12. traditional class-d modulation scheme's output voltage and current waveforms into an inductive load with no input the tpa2000d2 uses a modulation scheme that still has each output switching from 0 to the supply voltage. however, out+ and out- are now in phase with each other with no input. the duty cycle of out+ is greater than 50% and out- is less than 50% for positive voltages. the duty cycle of out+ is less than 50% and out- is greater than 50% for negative voltages. the voltage across the load sits at 0 volts throughout most of the switching period greatly reducing the switching current, which reduces any i 2 r losses in the load. 9 submit documentation feedback www.ti.com o v 5 v +5 v current out+ differential v oltage across load out
efficiency: why you must use a filter with the traditional class-d effects of applying a square wave into a speaker tpa2000d2 slos291f ? march 2000 ? revised march 2007 application information (continued) figure 13. the tpa2000d2 output voltage and current waveforms into an inductive load modulation scheme the main reason that the traditional class-d amplifier needs an output filter is that the switching waveform results in maximum current flow. this causes more loss in the load, which causes lower efficiency. the ripple current is large for the traditional modulation scheme because the ripple current is proportional to voltage multiplied by the time at that voltage. the differential voltage swing is 2 v dd and the time at each voltage is half the period for the traditional modulation scheme. an ideal lc filter is needed to store the ripple current from each half cycle for the next half cycle, while any resistance causes power dissipation. the speaker is both resistive and reactive, whereas an lc filter is almost purely reactive. the tpa2000d2 modulation scheme has very little loss in the load without a filter because the pulses are very short and the change in voltage is v dd instead of 2 v dd . as the output power increases, the pulses widen making the ripple current larger. ripple current could be filtered with an lc filter for increased efficiency, but for most applications the filter is not needed. an lc filter with a cutoff frequency less than the class-d switching frequency allows the switching current to flow through the filter instead of the load. the filter has less resistance than the speaker, which results in less power dissipated and increased efficiency. audio specialists have said for years not to apply a square wave to speakers. if the amplitude of the waveform is high enough and the frequency of the square wave is within the bandwidth of the speaker, the square wave could cause the voice coil to jump out of the air gap and/or scar the voice coil. a 250-khz switching frequency, however, is not significant because the speaker cone movement is proportional to 1/f 2 for frequencies beyond the audio band. therefore, the amount of cone movement at the switching frequency is very small. however, 10 submit documentation feedback www.ti.com 0 v 5 v +5 v current out+ out differential voltage across load 0 v 5 v +5 v current out+ out differential voltage across load output = 0 voutput > 0 v
(1) (2) (3) when to use an output filter gain setting via gain0 and gain1 inputs tpa2000d2 slos291f ? march 2000 ? revised march 2007 application information (continued) damage could occur to the speaker if the voice coil is not designed to handle the additional power. to size the speaker for added power, the ripple current dissipated in the load needs to be calculated by subtracting the theoretical supplied power, p sup theoretical , from the actual supply power, p sup , at maximum output power, p out . the switching power dissipated in the speaker is the inverse of the measured efficiency, h measured , minus the theoretical efficiency, h theoretical . the maximum efficiency of the tpa2000d2 with an 8- w load is 85%. using equation 3 with the efficiency at maximum power from figure 2 (78%), we see that there is an additional 106 mw dissipated in the speaker. the added power dissipated in the speaker is not an issue as long as it is taken into account when choosing the speaker. design the tpa2000d2 without the filter if the traces from amplifier to speaker are short. the tpa2000d2 passed fcc and ce radiated emissions with no shielding with speaker wires 8 inches (20,32 cm) long or less. notebook pcs and powered speakers where the speaker is in the same enclosure as the amplifier are good applications for class-d without a filter. a ferrite bead filter can often be used if the design is failing radiated emissions without a filter, and the frequency sensitive circuit is greater than 1 mhz. this is good for circuits that just have to pass fcc and ce because fcc and ce only test radiated emissions greater than 30 mhz. if choosing a ferrite bead, choose one with high impedance at high frequencies, but very low impedance at low frequencies. use an output filter if there are low frequency (< 1 mhz) emi sensitive circuits and/or there are long leads from amplifier to speaker. the gain of the tpa2000d2 is set by two input terminals, gain0 and gain1. the gains listed in table 2 are realized by changing the taps on the input resistors inside the amplifier. this causes the input impedance, z i , to be dependent on the gain setting. the actual gain settings are controlled by ratios of resistors, so the actual gain distribution from part-to-part is quite good. however, the input impedance may shift by 30% due to shifts in the actual resistance of the input resistors. for design purposes, the input network (discussed in the next section) should be designed assuming an input impedance of 20 k w , which is the absolute minimum input impedance of the tpa2000d2. at the lower gain settings, the input impedance could increase to as high as 115 k w . table 2. gain settings amplifier gain input impedance (db) (k w ) gain1 gain0 typ typ 0 0 8 104 0 1 12 74 1 0 17.5 44 1 1 23.5 24 11 submit documentation feedback www.ti.com p spkr = p sup p sup theoretical (at max output power) p spkr = p sup / p out p sup theoretical / p out (at max output power) p spkr = 1/ h measured 1/ h theoretical (at max output power)
input resistance (4) input capacitor, c i (5) (6) (7) tpa2000d2 slos291f ? march 2000 ? revised march 2007 each gain setting is achieved by varying the input resistance of the amplifier, which can range from its smallest value to over 6 times that value. the -3 db frequency can be calculated using equation 4 : in the typical application an input capacitor, c i , is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. in this case, c i and the input impedance of the amplifier, z i , form a high-pass filter with the corner frequency determined in equation 5 . the value of c i is important, as it directly affects the bass (low frequency) performance of the circuit. consider the example where z i is 20 k w and the specification calls for a flat bass response down to 80 hz. equation 5 is reconfigured as equation 6 . in this example, c i is 0.1 f, so one would likely choose a value in the range of 0.1 f to 1 f. if the gain is known and is constant, use z i from table 1 to calculate c i . a further consideration for this capacitor is the leakage path from the input source through the input network (c i ) and the feedback network to the load. this leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. for this reason a low-leakage tantalum or ceramic capacitor is the best choice. when polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most applications as the dc level there is held at v dd /2, which is likely higher than the source dc level. note that it is important to confirm the capacitor polarity in the application. c i should be 10 times smaller than the bypass capacitor to reduce clicking and popping noise from power on/off and entering and leaving shutdown. after sizing ci for a given cutoff frequency, size the bypass capacitor up to 10 times that of the input capacitor. 12 submit documentation feedback www.ti.com c i in z i z f input signal f 3 db 1 2 c i z i f c(highpass) 1 2 z i c i ?3 db f c c i 1 2 z i f c c i c byp / 10
switching frequency (8) power supply decoupling, c s midrail bypass capacitor, c byp (9) differential input shutdown modes tpa2000d2 slos291f ? march 2000 ? revised march 2007 the switching frequency is determined using the values of the components connected to r osc (pin 18) and c osc (pin 7) and is calculated with the following equation: the switching frequency was chosen to be centered on 250 khz. this frequency is the optimum audio fidelity of oversampling and of maximizing efficiency by minimizing the switching losses of the amplifier. the recommended values are a resistance of 120 k w and a capacitance of 220 pf. using these component values, the amplifier operates properly by using 5% tolerance resistors and 10% tolerance capacitors. the tolerance of the components can be changed, as long as the switching frequency remains between 200 khz and 300 khz. within this range, the internal circuitry of the device provides stable operation. the tpa2000d2 is a high-performance cmos audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (thd) is as low as possible. power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. the optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. for higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance (esr) ceramic capacitor, typically 0.1 f placed as close as possible to the device v dd lead works best. for filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 f or greater placed near the audio power amplifier is recommended. the midrail bypass capacitor, c byp , is the most critical capacitor and serves several important functions. during start-up or recovery from shutdown mode, c byp determines the rate at which the amplifier starts up. the second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. this noise is from the midrail generation circuit internal to the amplifier, which appears as degraded psrr and thd+n. bypass capacitor, c byp , values of 0.47 f to 1 f ceramic or tantalum low-esr capacitors are recommended for the best thd and noise performance. increasing the bypass capacitor reduces clicking and popping noise from power on/off and entering and leaving shutdown. to have minimal pop, c byp should be 10 times larger than c i . the differential input stage of the amplifier cancels any noise that appears on both input lines of a channel. to use the tpa2000d2 evm with a differential source, connect the positive lead of the audio source to the rinp (linp) input and the negative lead from the audio source to the rinn (linn) input. to use the tpa2000d2 with a single-ended source, ac ground the rinn and linn inputs through a capacitor and apply the audio single to the rinp and linp inputs. in a single-ended input application, the rinn and linn inputs should be ac-grounded at the audio source instead of at the device inputs for best noise performance. the tpa2000d2 employs a shutdown mode of operation designed to reduce supply current, i dd , to the absolute minimum level during periods of nonuse for battery-power conservation. the shutdown input terminal should be held high during normal operation when the amplifier is in use. pulling shutdown low causes the outputs to mute and the amplifier to enter a low-current state, i dd(sd) = 1 a. shutdown should never be left unconnected, because amplifier operation would be unpredictable. 13 submit documentation feedback www.ti.com f s 6.6 r osc c osc c byp 10 c i
using low-esr capacitors evaluation circuit tpa2000d2 slos291f ? march 2000 ? revised march 2007 low-esr capacitors are recommended throughout this application section. a real (as opposed to ideal) capacitor can be modeled simply as a resistor in series with an ideal capacitor. the voltage drop across this resistor minimizes the beneficial effects of the capacitor in the circuit. the lower the equivalent value of this resistance the more the real capacitor behaves like an ideal capacitor. table 3. tpa2000d2 application bill of materials reference description size quantity manufacturer part number c1-4, c17-21 capacitor, ceramic chip, 0.1 f, 10%, x7r, 50 v 0805 9 kemet c0805c104k5rac c5 capacitor, ceramic, 1.0 f, 80%/-20%, y5v, 16 v 0805 1 murata grm40-y5v105z16 c6, c8 capacitor, ceramic, 10 f, 80%/-20%, y5v, 16 v 1210 2 murata grm235-y5v106z16 c7 capacitor, ceramic, 220 pf, 10%, xicon, 50 v 0805 2 mouser 140-cc501b221k r1 resistor, chip, 120 k w , 1/10 w, 5%, xicon 0805 1 mouser 260-120k ic, tpa2000d2, audio power amplifier, 2-w, 24 pin u1 1 ti tpa2000d2pwp 2-channel, class-d tssop 14 submit documentation feedback www.ti.com right audio input+ to system control tpa2000d2 c7 220 pf c18 c2 c3 c4 left audio input+ c17 c1 c6 c5 left audio output+ c8 vddvdd right audio output r1 120k c19 c20 c21 0.1 m f 0.1 m f 0.1 m f 0.1 m f 0.1 m f 0.1 m f 1 m f 10 m f 0.1 m f 0.1 m f 0.1 m f shutdown pgndloutn gain0 lpvdd linn agnd cosc rinn rpvdd routn pgnd pgnd loutp bypass lpvdd linp vdd rosc rinp rpvdd gain1 routp pgnd 20 10 10 m f left audio input right audio input vdd vdd gain select gain select right audio output + left audio output
packaging information orderable device status (1) package type package drawing pins package qty eco plan (2) lead/ball finish msl peak temp (3) tpa2000d2pw active tssop pw 24 60 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tpa2000d2pwg4 active tssop pw 24 60 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tpa2000d2pwp active htssop pwp 24 60 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tpa2000d2pwpg4 active htssop pwp 24 60 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tpa2000d2pwpr active htssop pwp 24 2000 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tpa2000d2pwprg4 active htssop pwp 24 2000 green (rohs & no sb/br) cu nipdau level-2-260c-1 year tpa2000d2pwr active tssop pw 24 2000 green (rohs & no sb/br) cu nipdau level-2-260c-1 year TPA2000D2PWRG4 active tssop pw 24 2000 green (rohs & no sb/br) cu nipdau level-2-260c-1 year (1) the marketing status values are defined as follows: active: product device recommended for new designs. lifebuy: ti has announced that the device will be discontinued, and a lifetime-buy period is in effect. nrnd: not recommended for new designs. device is in production to support existing customers, but ti does not recommend using this part in a new design. preview: device has been announced but is not in production. samples may or may not be available. obsolete: ti has discontinued the production of the device. (2) eco plan - the planned eco-friendly classification: pb-free (rohs), pb-free (rohs exempt), or green (rohs & no sb/br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. tbd: the pb-free/green conversion plan has not been defined. pb-free (rohs): ti's terms "lead-free" or "pb-free" mean semiconductor products that are compatible with the current rohs requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. where designed to be soldered at high temperatures, ti pb-free products are suitable for use in specified lead-free processes. pb-free (rohs exempt): this component has a rohs exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. the component is otherwise considered pb-free (rohs compatible) as defined above. green (rohs & no sb/br): ti defines "green" to mean pb-free (rohs compatible), and free of bromine (br) and antimony (sb) based flame retardants (br or sb do not exceed 0.1% by weight in homogeneous material) (3) msl, peak temp. -- the moisture sensitivity level rating according to the jedec industry standard classifications, and peak solder temperature. important information and disclaimer: the information provided on this page represents ti's knowledge and belief as of the date that it is provided. ti bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. efforts are underway to better integrate information from third parties. ti has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. ti and ti suppliers consider certain information to be proprietary, and thus cas numbers and other limited information may not be available for release. in no event shall ti's liability arising out of such information exceed the total purchase price of the ti part(s) at issue in this document sold by ti to customer on an annual basis. package option addendum www.ti.com 18-apr-2006 addendum-page 1

mechanical data mtss001c january 1995 revised february 1999 post office box 655303 ? dallas, texas 75265 pw (r-pdso-g**) plastic small-outline package 14 pins shown 0,65 m 0,10 0,10 0,25 0,50 0,75 0,15 nom gage plane 28 9,80 9,60 24 7,90 7,70 20 16 6,60 6,40 4040064/f 01/97 0,30 6,60 6,20 8 0,19 4,30 4,50 7 0,15 14 a 1 1,20 max 14 5,10 4,90 8 3,10 2,90 a max a min dim pins ** 0,05 4,90 5,10 seating plane 0 8 notes: a. all linear dimensions are in millimeters. b. this drawing is subject to change without notice. c. body dimensions do not include mold flash or protrusion not to exceed 0,15. d. falls within jedec mo-153
important notice texas instruments incorporated and its subsidiaries (ti) reserve the right to make corrections, modifications, enhancements, improvements, and other changes to its products and services at any time and to discontinue any product or service without notice. cu stomers should obtain the latest relevant information before placing orders and should verify that such info rmation is current and complete. all products are sold subject to ti?s terms and conditions of sale supplied at the time of order acknowledgment. ti warrants performance of its hardware products to the specifications applicable at the time of sale in accordance with ti?s standard warranty. testing and othe r quality control techniques are used to the extent ti deems necessary to support this warranty. except where mandated by governm ent requirements, testing of all parameters of each product is not necessarily performed. ti assumes no liability for applications assistance or customer product design. customers are responsible for their products and applications using ti component s. to minimize the risks associated with customer products and applications, customers should provide adequate design and operating safeguards. ti does not warrant or represent that any license, either express or implie d, is granted under any ti patent right, copyright, mask work right, or other ti intellectual property right relating to any combination, machine, or process in which ti products or services are us ed. information published by ti regarding third-party products or services does not consti tute a license from ti to use such products or services or a warranty or endorsement thereof. use of such information may require a license from a third party under the patents or other intellectual property of the third party, or a license from ti under the pat ents or other intellectual property of ti. reproduction of information in ti data books or data sheets is permissible only if reproduction is without alteration and is accompanied by all associated warranties, conditions, lim itations, and notices. reproduction of this information with alteration is an unfair and deceptive business practice. ti is not responsible or liable for such altered documentation. resale of ti products or services with statements diffe rent from or beyond the parameters stated by ti for that product or service voids all express and any imp lied warranties for the associated ti product or service and is an unfair and deceptive business practice. ti is not responsible or liable for any such statements. following are urls where you can obtain information on other texas instruments products and application solutions: products applications amplifiers amplifier.ti.c om audio www.ti.com/audio data converters dataconverter.ti.co m automotive www.ti.com/automotive dsp dsp.ti.com broadband www.ti.com/broadband interface interface.ti.com digital control www.ti.com/digitalcontrol logic logic.ti.com military www.ti.com/military power mgmt power.ti.com optical networking www.ti.com/opticalnetwork microcontrollers microcontroller.ti.com security www.ti.com/security low power wireless www.ti.com/lpw telephony www.ti.com/telephony video & imaging www.ti.com/video wireless www.ti.com/wireless mailing address: texas instruments post office box 6553 03 dallas, texas 75265 copyright ? 2007, texas instruments incorporated

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